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Versions: (draft-ietf-codec-harmony) 00 01 02 03 04 05 06 07 08 09 10 11 12 13 14 15 16 RFC 6716

Network Working Group                                          JM. Valin
Internet-Draft                                              Octasic Inc.
Intended status: Standards Track                                  K. Vos
Expires: August 8, 2011                          Skype Technologies S.A.
                                                        February 4, 2011


                   Definition of the Opus Audio Codec
                        draft-ietf-codec-opus-02

Abstract

   This document describes the Opus codec, designed for interactive
   speech and audio transmission over the Internet.

Status of this Memo

   This Internet-Draft is submitted in full conformance with the
   provisions of BCP 78 and BCP 79.

   Internet-Drafts are working documents of the Internet Engineering
   Task Force (IETF).  Note that other groups may also distribute
   working documents as Internet-Drafts.  The list of current Internet-
   Drafts is at http://datatracker.ietf.org/drafts/current/.

   Internet-Drafts are draft documents valid for a maximum of six months
   and may be updated, replaced, or obsoleted by other documents at any
   time.  It is inappropriate to use Internet-Drafts as reference
   material or to cite them other than as "work in progress."

   This Internet-Draft will expire on August 8, 2011.

Copyright Notice

   Copyright (c) 2011 IETF Trust and the persons identified as the
   document authors.  All rights reserved.

   This document is subject to BCP 78 and the IETF Trust's Legal
   Provisions Relating to IETF Documents
   (http://trustee.ietf.org/license-info) in effect on the date of
   publication of this document.  Please review these documents
   carefully, as they describe your rights and restrictions with respect
   to this document.  Code Components extracted from this document must
   include Simplified BSD License text as described in Section 4.e of
   the Trust Legal Provisions and are provided without warranty as
   described in the Simplified BSD License.





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Table of Contents

   1.  Introduction  . . . . . . . . . . . . . . . . . . . . . . . .   4
   2.  Opus Codec  . . . . . . . . . . . . . . . . . . . . . . . . .   5
     2.1.  Source Code . . . . . . . . . . . . . . . . . . . . . . .   5
   3.  Codec Modes . . . . . . . . . . . . . . . . . . . . . . . . .   6
     3.1.  Examples  . . . . . . . . . . . . . . . . . . . . . . . .   7
   4.  Codec Encoder . . . . . . . . . . . . . . . . . . . . . . . .   9
     4.1.  Range Coder . . . . . . . . . . . . . . . . . . . . . . .   9
       4.1.1.  Encoding Symbols  . . . . . . . . . . . . . . . . . .   9
       4.1.2.  Encoding Uniformly Distributed Integers . . . . . . .  10
       4.1.3.  Finalizing the Stream . . . . . . . . . . . . . . . .  11
       4.1.4.  Current Bit Usage . . . . . . . . . . . . . . . . . .  11
     4.2.  SILK Encoder  . . . . . . . . . . . . . . . . . . . . . .  11
       4.2.1.  Voice Activity Detection  . . . . . . . . . . . . . .  13
       4.2.2.  High-Pass Filter  . . . . . . . . . . . . . . . . . .  13
       4.2.3.  Pitch Analysis  . . . . . . . . . . . . . . . . . . .  14
       4.2.4.  Noise Shaping Analysis  . . . . . . . . . . . . . . .  15
       4.2.5.  Prefilter . . . . . . . . . . . . . . . . . . . . . .  19
       4.2.6.  Prediction Analysis . . . . . . . . . . . . . . . . .  20
       4.2.7.  LSF Quantization  . . . . . . . . . . . . . . . . . .  20
       4.2.8.  LTP Quantization  . . . . . . . . . . . . . . . . . .  23
       4.2.9.  Noise Shaping Quantizer . . . . . . . . . . . . . . .  24
       4.2.10. Range Encoder . . . . . . . . . . . . . . . . . . . .  25
     4.3.  CELT Encoder  . . . . . . . . . . . . . . . . . . . . . .  25
       4.3.1.  Forward MDCT  . . . . . . . . . . . . . . . . . . . .  25
       4.3.2.  Bands and Normalization . . . . . . . . . . . . . . .  26
       4.3.3.  Energy Envelope Quantization  . . . . . . . . . . . .  26
       4.3.4.  Bit Allocation  . . . . . . . . . . . . . . . . . . .  27
       4.3.5.  Pitch Prediction  . . . . . . . . . . . . . . . . . .  28
       4.3.6.  Spherical Vector Quantization . . . . . . . . . . . .  28
       4.3.7.  Stereo support  . . . . . . . . . . . . . . . . . . .  30
       4.3.8.  Synthesis . . . . . . . . . . . . . . . . . . . . . .  31
       4.3.9.  Variable Bitrate (VBR)  . . . . . . . . . . . . . . .  32
   5.  Codec Decoder . . . . . . . . . . . . . . . . . . . . . . . .  33
     5.1.  Range Decoder . . . . . . . . . . . . . . . . . . . . . .  33
       5.1.1.  Decoding Symbols  . . . . . . . . . . . . . . . . . .  33
       5.1.2.  Decoding Uniformly Distributed Integers . . . . . . .  34
       5.1.3.  Current Bit Usage . . . . . . . . . . . . . . . . . .  34
     5.2.  SILK Decoder  . . . . . . . . . . . . . . . . . . . . . .  35
       5.2.1.  Decoder Modules . . . . . . . . . . . . . . . . . . .  35
     5.3.  CELT Decoder  . . . . . . . . . . . . . . . . . . . . . .  37
       5.3.1.  Energy Envelope Decoding  . . . . . . . . . . . . . .  37
       5.3.2.  Pitch prediction decoding . . . . . . . . . . . . . .  37
       5.3.3.  Spherical VQ Decoder  . . . . . . . . . . . . . . . .  38
       5.3.4.  Denormalization . . . . . . . . . . . . . . . . . . .  38
       5.3.5.  Inverse MDCT  . . . . . . . . . . . . . . . . . . . .  38
       5.3.6.  Packet Loss Concealment (PLC) . . . . . . . . . . . .  38



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   6.  Security Considerations . . . . . . . . . . . . . . . . . . .  40
   7.  IANA Considerations . . . . . . . . . . . . . . . . . . . . .  41
   8.  Acknowledgments . . . . . . . . . . . . . . . . . . . . . . .  42
   9.  Informative References  . . . . . . . . . . . . . . . . . . .  43
   Appendix A.  Reference Implementation . . . . . . . . . . . . . .  45
     A.1.  Extracting the source . . . . . . . . . . . . . . . . . .  45
     A.2.  Base64-encoded source code  . . . . . . . . . . . . . . .  45
   Authors' Addresses  . . . . . . . . . . . . . . . . . . . . . . . 185











































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1.  Introduction

   We propose the Opus codec based on a linear prediction layer (LP) and
   an MDCT-based enhancement layer.  The main idea behind the proposal
   is that the speech low frequencies are usually more efficiently coded
   using linear prediction codecs (such as CELP variants), while the
   higher frequencies are more efficiently coded in the transform domain
   (e.g.  MDCT).  For low sampling rates, the MDCT layer is not useful
   and only the LP-based layer is used.  On the other hand, non-speech
   signals are not always adequately coded using linear prediction, so
   for music only the MDCT-based layer is used.

   In this proposed prototype, the LP layer is based on the SILK [1]
   codec [SILK] and the MDCT layer is based on the CELT [2] codec
   [CELT].

   This is a work in progress.


































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2.  Opus Codec

   In hybrid mode, each frame is coded first by the LP layer and then by
   the MDCT layer.  In the current prototype, the cutoff frequency is 8
   kHz.  In the MDCT layer, all bands below 8 kHz are discarded, such
   that there is no coding redundancy between the two layers.  Also both
   layers use the same instance of the range coder to encode the signal,
   which ensures that no "padding bits" are wasted.  The hybrid approach
   makes it easy to support both constant bit-rate (CBR) and varaible
   bit-rate (VBR) coding.  Although the SILK layer used is VBR, it is
   easy to make the bit allocation of the CELT layer produce a final
   stream that is CBR by using all the bits left unused by the SILK
   layer.

   The implementation of SILK-based LP layer is similar to the
   description in the SILK Internet-Draft [SILK] with the main exception
   that SILK was modified to use the same range coder as CELT.  The
   implementation of the CELT-based MDCT layer is available from the
   CELT website and is a more recent version (0.8.1) of the CELT
   Internet-Draft [CELT].  The main changes include better support for
   20 ms frames as well as the ability to encode only the higher bands
   using a range coder partially filled by the SILK layer.

   In addition to their frame size, the SILK and CELT codecs require a
   look-ahead of 5.2 ms and 2.5 ms, respectively.  SILK's look-ahead is
   due to noise shaping estimation (5 ms) and the internal resampling
   (0.2 ms), while CELT's look-ahead is due to the overlapping MDCT
   windows.  To compensate for the difference, the CELT encoder input is
   delayed by 2.7 ms.  This ensures that low frequencies and high
   frequencies arrive at the same time.

2.1.  Source Code

   The source code is currently available in a Git repository [3] which
   references two other repositories (for SILK and CELT).  Some
   snapshots are provided for convenience at
   <http://people.xiph.org/~jm/ietfcodec/> along with sample files.
   Although the build system is very primitive, some instructions are
   provided in the toplevel README file.  This is very early development
   so both the quality and feature set should greatly improve over time.
   In the current version, only 48 kHz audio is supported, but support
   for all configurations listed in Section 3 is planned.









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3.  Codec Modes

   There are three possible operating modes for the proposed prototype:

   1.  A linear prediction (LP) mode for use in low bit-rate connections
       with up to 8 kHz audio bandwidth (16 kHz sampling rate)

   2.  A hybrid (LP+MDCT) mode for full-bandwidth speech at medium
       bitrates

   3.  An MDCT-only mode for very low delay speech transmission as well
       as music transmission.

   Each of these modes supports a number of difference frame sizes and
   sampling rates.  In order to distinguish between the various modes
   and configurations, we define a single-byte table-of-contents (TOC)
   header that can used in the transport layer (e.g RTP) to signal this
   information.  The following describes the proposed TOC byte.

   The LP mode supports the following configurations (numbered from 0 to
   11):

   o  8 kHz: 10, 20, 40, 60 ms (0..3)

   o  12 kHz: 10, 20, 40, 60 ms (4..7)

   o  16 kHz: 10, 20, 40, 60 ms (8..11)

   for a total of 12 configurations.

   The hybrid mode supports the following configurations (numbered from
   12 to 15):

   o  32 kHz: 10, 20 ms (12..13)

   o  48 kHz: 10, 20 ms (14..15)

   for a total of 4 configurations.

   The MDCT-only mode supports the following configurations (numbered
   from 16 to 31):

   o  8 kHz: 2.5, 5, 10, 20 ms (16..19)

   o  16 kHz: 2.5, 5, 10, 20 ms (20..23)

   o  32 kHz: 2.5, 5, 10, 20 ms (24..27)




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   o  48 kHz: 2.5, 5, 10, 20 ms (28..31)

   for a total of 16 configurations.

   There is thus a total of 32 configurations, encoded in 5 bits.  On
   bit is used to signal mono vs stereo, which leaves 2 bits for the
   number of frames per packets (codes 0 to 3):

   o  0: 1 frames in the packet

   o  1: 2 frames in the packet, each with equal compressed size

   o  2: 2 frames in the packet, with different compressed size

   o  3: arbitrary number of frames in the packet

   For code 2, the TOC byte is followed by the length of the first
   frame, encoded as described below.  For code 3, the TOC byte is
   followed by a byte encoding the number of frames in the packet, with
   the MSB indicating VBR.  In the VBR case, the byte indicating the
   number of frames is followed by N-1 frame lengths encoded as
   described below.  As an additional limit, the audio duration
   contained within a packet may not exceed 120 ms.

   The compressed size of the frames (if needed) is indicated -- usually
   -- with one byte, with the following meaning:

   o  0: No frame (DTX or lost packet)

   o  1-251: Size of the frame in bytes

   o  252-255: A second byte is needed.  The total size is (size[1]*4)+
      size[0]

   The maximum size representable is 255*4+255=1275 bytes.  For 20 ms
   frames, that represents a bit-rate of 510 kb/s, which is really the
   highest rate anyone would want to use in stereo mode (beyond that
   point, lossless codecs would be more appropriate).

3.1.  Examples

   Simplest case: one narrowband mono 20-ms SILK frame


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    1    |0|0|0|               compressed data...              |



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   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Two 48 kHz mono 5 ms CELT frames of the same compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    29   |0|0|1|               compressed data...              |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Two 48 kHz mono 20-ms hybrid frames of different compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    15   |0|1|1|       2       |   frame size  |compressed data|
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |                       compressed data...                      |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Four 48 kHz stereo 20-ms CELT frame of the same compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    31   |1|1|0|       4       |      compressed data...       |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+





















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4.  Codec Encoder

   Opus encoder block diagram.

4.1.  Range Coder

   Opus uses an entropy coder based upon [range-coding], which is itself
   a rediscovery of the FIFO arithmetic code introduced by
   [coding-thesis].  It is very similar to arithmetic encoding, except
   that encoding is done with digits in any base instead of with bits,
   so it is faster when using larger bases (i.e.: an octet).  All of the
   calculations in the range coder must use bit-exact integer
   arithmetic.

   The range coder also acts as the bit-packer for Opus.  It is used in
   three different ways, to encode:

   o  entropy-coded symbols with a fixed probability model using
      ec_encode(), (rangeenc.c)

   o  integers from 0 to 2^M-1 using ec_enc_uint() or ec_enc_bits(),
      (entenc.c)

   o  integers from 0 to N-1 (where N is not a power of two) using
      ec_enc_uint(). (entenc.c)

   The range encoder maintains an internal state vector composed of the
   four-tuple (low,rng,rem,ext), representing the low end of the current
   range, the size of the current range, a single buffered output octet,
   and a count of additional carry-propagating output octets.  Both rng
   and low are 32-bit unsigned integer values, rem is an octet value or
   the special value -1, and ext is an integer with at least 16 bits.
   This state vector is initialized at the start of each each frame to
   the value (0,2^31,-1,0).

   Each symbol is drawn from a finite alphabet and coded in a separate
   context which describes the size of the alphabet and the relative
   frequency of each symbol in that alphabet.  Opus only uses static
   contexts; they are not adapted to the statistics of the data that is
   coded.

4.1.1.  Encoding Symbols

   The main encoding function is ec_encode() (rangeenc.c), which takes
   as an argument a three-tuple (fl,fh,ft) describing the range of the
   symbol to be encoded in the current context, with 0 <= fl < fh <= ft
   <= 65535.  The values of this tuple are derived from the probability
   model for the symbol.  Let f(i) be the frequency of the ith symbol in



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   the current context.  Then the three-tuple corresponding to the kth
   symbol is given by fl=sum(f(i),i<k), fh=fl+f(i), and ft=sum(f(i)).

   ec_encode() updates the state of the encoder as follows.  If fl is
   greater than zero, then low = low + rng - (rng/ft)*(ft-fl) and rng =
   (rng/ft)*(fh-fl).  Otherwise, low is unchanged and rng = rng - (rng/
   ft)*(fh-fl).  The divisions here are exact integer division.  After
   this update, the range is normalized.

   To normalize the range, the following process is repeated until rng >
   2^23.  First, the top 9 bits of low, (low>>23), are placed into a
   carry buffer.  Then, low is set to (low << 8 & 0x7FFFFFFF) and rng is
   set to (rng<<8).  This process is carried out by ec_enc_normalize()
   (rangeenc.c).

   The 9 bits produced in each iteration of the normalization loop
   consist of 8 data bits and a carry flag.  The final value of the
   output bits is not determined until carry propagation is accounted
   for.  Therefore the reference implementation buffers a single (non-
   propagating) output octet and keeps a count of additional propagating
   (0xFF) output octets.  An implementation MAY choose to use any
   mathematically equivalent scheme to perform carry propagation.

   The function ec_enc_carry_out() (rangeenc.c) performs this buffering.
   It takes a 9-bit input value, c, from the normalization 8-bit output
   and a carry bit.  If c is 0xFF, then ext is incremented and no octets
   are output.  Otherwise, if rem is not the special value -1, then the
   octet (rem+(c>>8)) is output.  Then ext octets are output with the
   value 0 if the carry bit is set, or 0xFF if it is not, and rem is set
   to the lower 8 bits of c.  After this, ext is set to zero.

   In the reference implementation, a special version of ec_encode()
   called ec_encode_bin() (rangeenc.c) is defined to take a two-tuple
   (fl,ftb), where 0 <= fl < 2^ftb and ftb < 16.  It is mathematically
   equivalent to calling ec_encode() with the three-tuple (fl,fl+
   1,1<<ftb), but avoids using division.

4.1.2.  Encoding Uniformly Distributed Integers

   Functions ec_enc_uint() or ec_enc_bits() are based on ec_encode() and
   encode one of N equiprobable symbols, each with a frequency of 1,
   where N may be as large as 2^32-1.  Because ec_encode() is limited to
   a total frequency of 2^16-1, this is done by encoding a series of
   symbols in smaller contexts.

   ec_enc_bits() (entenc.c) is defined, like ec_encode_bin(), to take a
   two-tuple (fl,ftb), with 0 <= fl < 2^ftb and ftb < 32.  While ftb is
   greater than 8, it encodes bits (ftb-8) to (ftb-1) of fl, e.g.,



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   (fl>>ftb-8&0xFF) using ec_encode_bin() and subtracts 8 from ftb.
   Then, it encodes the remaining bits of fl, e.g., (fl&(1<<ftb)-1),
   again using ec_encode_bin().

   ec_enc_uint() (entenc.c) takes a two-tuple (fl,ft), where ft is not
   necessarily a power of two.  Let ftb be the location of the highest 1
   bit in the two's-complement representation of (ft-1), or -1 if no
   bits are set.  If ftb>8, then the top 8 bits of fl are encoded using
   ec_encode() with the three-tuple (fl>>ftb-8,(fl>>ftb-8)+
   1,(ft-1>>ftb-8)+1), and the remaining bits are encoded with
   ec_enc_bits using the two-tuple (fl&(1<<ftb-8)-1,ftb-8).  Otherwise,
   fl is encoded with ec_encode() directly using the three-tuple (fl,fl+
   1,ft).

4.1.3.  Finalizing the Stream

   After all symbols are encoded, the stream must be finalized by
   outputting a value inside the current range.  Let end be the integer
   in the interval [low,low+rng) with the largest number of trailing
   zero bits.  Then while end is not zero, the top 9 bits of end, e.g.,
   (end>>23), are sent to the carry buffer, and end is replaced by
   (end<<8&0x7FFFFFFF).  Finally, if the value in carry buffer, rem, is
   neither zero nor the special value -1, or the carry count, ext, is
   greater than zero, then 9 zero bits are sent to the carry buffer.
   After the carry buffer is finished outputting octets, the rest of the
   output buffer is padded with zero octets.  Finally, rem is set to the
   special value -1.  This process is implemented by ec_enc_done()
   (rangeenc.c).

4.1.4.  Current Bit Usage

   The bit allocation routines in Opus need to be able to determine a
   conservative upper bound on the number of bits that have been used to
   encode the current frame thus far.  This drives allocation decisions
   and ensures that the range code will not overflow the output buffer.
   This is computed in the reference implementation to fractional bit
   precision by the function ec_enc_tell() (rangeenc.c).  Like all
   operations in the range encoder, it must be implemented in a bit-
   exact manner.

4.2.  SILK Encoder

   In the following, we focus on the core encoder and describe its
   components.  For simplicity, we will refer to the core encoder simply
   as the encoder in the remainder of this document.  An overview of the
   encoder is given in Figure 1.





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                                                                 +---+
                                  +----------------------------->|   |
           +---------+            |     +---------+              |   |
           |Voice    |            |     |LTP      |              |   |
    +----->|Activity |-----+      +---->|Scaling  |---------+--->|   |
    |      |Detector |  3  |      |     |Control  |<+  12   |    |   |
    |      +---------+     |      |     +---------+ |       |    |   |
    |                      |      |     +---------+ |       |    |   |
    |                      |      |     |Gains    | |  11   |    |   |
    |                      |      |  +->|Processor|-|---+---|--->| R |
    |                      |      |  |  |         | |   |   |    | a |
    |                     \/      |  |  +---------+ |   |   |    | n |
    |                 +---------+ |  |  +---------+ |   |   |    | g |
    |                 |Pitch    | |  |  |LSF      | |   |   |    | e |
    |              +->|Analysis |-+  |  |Quantizer|-|---|---|--->|   |
    |              |  |         |4|  |  |         | | 8 |   |    | E |->
    |              |  +---------+ |  |  +---------+ |   |   |    | n |14
    |              |              |  |   9/\  10|   |   |   |    | c |
    |              |              |  |    |    \/   |   |   |    | o |
    |              |  +---------+ |  |  +----------+|   |   |    | d |
    |              |  |Noise    | +--|->|Prediction|+---|---|--->| e |
    |              +->|Shaping  |-|--+  |Analysis  || 7 |   |    | r |
    |              |  |Analysis |5|  |  |          ||   |   |    |   |
    |              |  +---------+ |  |  +----------+|   |   |    |   |
    |              |              |  |       /\     |   |   |    |   |
    |              |    +---------|--|-------+      |   |   |    |   |
    |              |    |        \/  \/            \/  \/  \/    |   |
    |  +---------+ |    |      +---------+       +------------+  |   |
    |  |High-Pass| |    |      |         |       |Noise       |  |   |
   -+->|Filter   |-+----+----->|Prefilter|------>|Shaping     |->|   |
   1   |         |      2      |         |   6   |Quantization|13|   |
       +---------+             +---------+       +------------+  +---+

   1:  Input speech signal
   2:  High passed input signal
   3:  Voice activity estimate
   4:  Pitch lags (per 5 ms) and voicing decision (per 20 ms)
   5:  Noise shaping quantization coefficients
     - Short term synthesis and analysis
       noise shaping coefficients (per 5 ms)
     - Long term synthesis and analysis noise
       shaping coefficients (per 5 ms and for voiced speech only)
     - Noise shaping tilt (per 5 ms)
     - Quantizer gain/step size (per 5 ms)
   6:  Input signal filtered with analysis noise shaping filters
   7:  Short and long term prediction coefficients
       LTP (per 5 ms) and LPC (per 20 ms)
   8:  LSF quantization indices



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   9:  LSF coefficients
   10: Quantized LSF coefficients
   11: Processed gains, and synthesis noise shape coefficients
   12: LTP state scaling coefficient. Controlling error propagation
      / prediction gain trade-off
   13: Quantized signal
   14: Range encoded bitstream



                          Encoder block diagram.

                                 Figure 1

4.2.1.  Voice Activity Detection

   The input signal is processed by a VAD (Voice Activity Detector) to
   produce a measure of voice activity, and also spectral tilt and
   signal-to-noise estimates, for each frame.  The VAD uses a sequence
   of half-band filterbanks to split the signal in four subbands: 0 -
   Fs/16, Fs/16 - Fs/8, Fs/8 - Fs/4, and Fs/4 - Fs/2, where Fs is the
   sampling frequency, that is, 8, 12, 16 or 24 kHz.  The lowest
   subband, from 0 - Fs/16 is high-pass filtered with a first-order MA
   (Moving Average) filter (with transfer function H(z) = 1-z^(-1)) to
   reduce the energy at the lowest frequencies.  For each frame, the
   signal energy per subband is computed.  In each subband, a noise
   level estimator tracks the background noise level and an SNR (Signal-
   to-Noise Ratio) value is computed as the logarithm of the ratio of
   energy to noise level.  Using these intermediate variables, the
   following parameters are calculated for use in other SILK modules:

   o  Average SNR.  The average of the subband SNR values.

   o  Smoothed subband SNRs.  Temporally smoothed subband SNR values.

   o  Speech activity level.  Based on the average SNR and a weighted
      average of the subband energies.

   o  Spectral tilt.  A weighted average of the subband SNRs, with
      positive weights for the low subbands and negative weights for the
      high subbands.

4.2.2.  High-Pass Filter

   The input signal is filtered by a high-pass filter to remove the
   lowest part of the spectrum that contains little speech energy and
   may contain background noise.  This is a second order ARMA (Auto
   Regressive Moving Average) filter with a cut-off frequency around 70



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   Hz.

   In the future, a music detector may also be used to lower the cut-off
   frequency when the input signal is detected to be music rather than
   speech.

4.2.3.  Pitch Analysis

   The high-passed input signal is processed by the open loop pitch
   estimator shown in Figure 2.


                                    +--------+  +----------+
                                    |2 x Down|  |Time-     |
                                 +->|sampling|->|Correlator|     |
                                 |  |        |  |          |     |4
                                 |  +--------+  +----------+    \/
                                 |                    | 2    +-------+
                                 |                    |  +-->|Speech |5
       +---------+    +--------+ |                   \/  |   |Type   |->
       |LPC      |    |Down    | |              +----------+ |       |
    +->|Analysis | +->|sample  |-+------------->|Time-     | +-------+
    |  |         | |  |to 8 kHz|                |Correlator|----------->
    |  +---------+ |  +--------+                |__________|          6
    |       |      |                                  |3
    |      \/      |                                 \/
    |  +---------+ |                            +----------+
    |  |Whitening| |                            |Time-     |
   -+->|Filter   |-+--------------------------->|Correlator|----------->
   1   |         |                              |          |          7
       +---------+                              +----------+

   1: Input signal
   2: Lag candidates from stage 1
   3: Lag candidates from stage 2
   4: Correlation threshold
   5: Voiced/unvoiced flag
   6: Pitch correlation
   7: Pitch lags


                   Block diagram of the pitch estimator.

                                 Figure 2

   The pitch analysis finds a binary voiced/unvoiced classification,
   and, for frames classified as voiced, four pitch lags per frame - one
   for each 5 ms subframe - and a pitch correlation indicating the



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   periodicity of the signal.  The input is first whitened using a
   Linear Prediction (LP) whitening filter, where the coefficients are
   computed through standard Linear Prediction Coding (LPC) analysis.
   The order of the whitening filter is 16 for best results, but is
   reduced to 12 for medium complexity and 8 for low complexity modes.
   The whitened signal is analyzed to find pitch lags for which the time
   correlation is high.  The analysis consists of three stages for
   reducing the complexity:

   o  In the first stage, the whitened signal is downsampled to 4 kHz
      (from 8 kHz) and the current frame is correlated to a signal
      delayed by a range of lags, starting from a shortest lag
      corresponding to 500 Hz, to a longest lag corresponding to 56 Hz.

   o  The second stage operates on a 8 kHz signal ( downsampled from 12,
      16 or 24 kHz ) and measures time correlations only near the lags
      corresponding to those that had sufficiently high correlations in
      the first stage.  The resulting correlations are adjusted for a
      small bias towards short lags to avoid ending up with a multiple
      of the true pitch lag.  The highest adjusted correlation is
      compared to a threshold depending on:

      *  Whether the previous frame was classified as voiced

      *  The speech activity level

      *  The spectral tilt.

      If the threshold is exceeded, the current frame is classified as
      voiced and the lag with the highest adjusted correlation is stored
      for a final pitch analysis of the highest precision in the third
      stage.

   o  The last stage operates directly on the whitened input signal to
      compute time correlations for each of the four subframes
      independently in a narrow range around the lag with highest
      correlation from the second stage.

4.2.4.  Noise Shaping Analysis

   The noise shaping analysis finds gains and filter coefficients used
   in the prefilter and noise shaping quantizer.  These parameters are
   chosen such that they will fulfil several requirements:

   o  Balancing quantization noise and bitrate.  The quantization gains
      determine the step size between reconstruction levels of the
      excitation signal.  Therefore, increasing the quantization gain
      amplifies quantization noise, but also reduces the bitrate by



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      lowering the entropy of the quantization indices.

   o  Spectral shaping of the quantization noise; the noise shaping
      quantizer is capable of reducing quantization noise in some parts
      of the spectrum at the cost of increased noise in other parts
      without substantially changing the bitrate.  By shaping the noise
      such that it follows the signal spectrum, it becomes less audible.
      In practice, best results are obtained by making the shape of the
      noise spectrum slightly flatter than the signal spectrum.

   o  Deemphasizing spectral valleys; by using different coefficients in
      the analysis and synthesis part of the prefilter and noise shaping
      quantizer, the levels of the spectral valleys can be decreased
      relative to the levels of the spectral peaks such as speech
      formants and harmonics.  This reduces the entropy of the signal,
      which is the difference between the coded signal and the
      quantization noise, thus lowering the bitrate.

   o  Matching the levels of the decoded speech formants to the levels
      of the original speech formants; an adjustment gain and a first
      order tilt coefficient are computed to compensate for the effect
      of the noise shaping quantization on the level and spectral tilt.



                 / \   ___
                  |   // \\
                  |  //   \\     ____
                  |_//     \\___//  \\         ____
                  | /  ___  \   /    \\       //  \\
                P |/  /   \  \_/      \\_____//    \\
                o |  /     \     ____  \     /      \\
                w | /       \___/    \  \___/  ____  \\___ 1
                e |/                  \       /    \  \
                r |                    \_____/      \  \__ 2
                  |                                  \
                  |                                   \___ 3
                  |
                  +---------------------------------------->
                                   Frequency

               1: Input signal spectrum
               2: Deemphasized and level matched spectrum
               3: Quantization noise spectrum


           Noise shaping and spectral de-emphasis illustration.




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                                 Figure 3

   Figure 3 shows an example of an input signal spectrum (1).  After de-
   emphasis and level matching, the spectrum has deeper valleys (2).
   The quantization noise spectrum (3) more or less follows the input
   signal spectrum, while having slightly less pronounced peaks.  The
   entropy, which provides a lower bound on the bitrate for encoding the
   excitation signal, is proportional to the area between the
   deemphasized spectrum (2) and the quantization noise spectrum (3).
   Without de-emphasis, the entropy is proportional to the area between
   input spectrum (1) and quantization noise (3) - clearly higher.

   The transformation from input signal to deemphasized signal can be
   described as a filtering operation with a filter


                                                    Wana(z)
               H(z) = G * ( 1 - c_tilt * z^(-1) ) * -------
                                                    Wsyn(z),


   having an adjustment gain G, a first order tilt adjustment filter
   with tilt coefficient c_tilt, and where


                   16                                 d
                   __                                __
    Wana(z) = (1 - \ (a_ana(k) * z^(-k))*(1 - z^(-L) \ b_ana(k)*z^(-k)),
                   /_                                /_
                   k=1                               k=-d


   is the analysis part of the de-emphasis filter, consisting of the
   short-term shaping filter with coefficients a_ana(k), and the long-
   term shaping filter with coefficients b_ana(k) and pitch lag L. The
   parameter d determines the number of long-term shaping filter taps.

   Similarly, but without the tilt adjustment, the synthesis part can be
   written as


                   16                                 d
                   __                                __
    Wsyn(z) = (1 - \ (a_syn(k) * z^(-k))*(1 - z^(-L) \ b_syn(k)*z^(-k)).
                   /_                                /_
                   k=1                               k=-d





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   All noise shaping parameters are computed and applied per subframe of
   5 milliseconds.  First, an LPC analysis is performed on a windowed
   signal block of 15 milliseconds.  The signal block has a look-ahead
   of 5 milliseconds relative to the current subframe, and the window is
   an asymmetric sine window.  The LPC analysis is done with the
   autocorrelation method, with an order of 16 for best quality or 12 in
   low complexity operation.  The quantization gain is found as the
   square-root of the residual energy from the LPC analysis, multiplied
   by a value inversely proportional to the coding quality control
   parameter and the pitch correlation.

   Next we find the two sets of short-term noise shaping coefficients
   a_ana(k) and a_syn(k), by applying different amounts of bandwidth
   expansion to the coefficients found in the LPC analysis.  This
   bandwidth expansion moves the roots of the LPC polynomial towards the
   origo, using the formulas


                         a_ana(k) = a(k)*g_ana^k, and
                         a_syn(k) = a(k)*g_syn^k,


   where a(k) is the k'th LPC coefficient and the bandwidth expansion
   factors g_ana and g_syn are calculated as


                         g_ana = 0.94 - 0.02*C, and
                         g_syn = 0.94 + 0.02*C,


   where C is the coding quality control parameter between 0 and 1.
   Applying more bandwidth expansion to the analysis part than to the
   synthesis part gives the desired de-emphasis of spectral valleys in
   between formants.

   The long-term shaping is applied only during voiced frames.  It uses
   three filter taps, described by


                   b_ana = F_ana * [0.25, 0.5, 0.25], and
                   b_syn = F_syn * [0.25, 0.5, 0.25].


   For unvoiced frames these coefficients are set to 0.  The
   multiplication factors F_ana and F_syn are chosen between 0 and 1,
   depending on the coding quality control parameter, as well as the
   calculated pitch correlation and smoothed subband SNR of the lowest
   subband.  By having F_ana less than F_syn, the pitch harmonics are



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   emphasized relative to the valleys in between the harmonics.

   The tilt coefficient c_tilt is for unvoiced frames chosen as


                          c_tilt = 0.4, and as
                          c_tilt = 0.04 + 0.06 * C


   for voiced frames, where C again is the coding quality control
   parameter and is between 0 and 1.

   The adjustment gain G serves to correct any level mismatch between
   original and decoded signal that might arise from the noise shaping
   and de-emphasis.  This gain is computed as the ratio of the
   prediction gain of the short-term analysis and synthesis filter
   coefficients.  The prediction gain of an LPC synthesis filter is the
   square-root of the output energy when the filter is excited by a
   unit-energy impulse on the input.  An efficient way to compute the
   prediction gain is by first computing the reflection coefficients
   from the LPC coefficients through the step-down algorithm, and
   extracting the prediction gain from the reflection coefficients as


                                 K
                                ___
                   predGain = ( | | 1 - (r_k)^2 )^(-0.5),
                                k=1


   where r_k is the k'th reflection coefficient.

   Initial values for the quantization gains are computed as the square-
   root of the residual energy of the LPC analysis, adjusted by the
   coding quality control parameter.  These quantization gains are later
   adjusted based on the results of the prediction analysis.

4.2.5.  Prefilter

   In the prefilter the input signal is filtered using the spectral
   valley de-emphasis filter coefficients from the noise shaping
   analysis, see Section 4.2.4.  By applying only the noise shaping
   analysis filter to the input signal, it provides the input to the
   noise shaping quantizer.







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4.2.6.  Prediction Analysis

   The prediction analysis is performed in one of two ways depending on
   how the pitch estimator classified the frame.  The processing for
   voiced and unvoiced speech are described in Section 4.2.6.1 and
   Section 4.2.6.2, respectively.  Inputs to this function include the
   pre-whitened signal from the pitch estimator, see Section 4.2.3.

4.2.6.1.  Voiced Speech

   For a frame of voiced speech the pitch pulses will remain dominant in
   the pre-whitened input signal.  Further whitening is desirable as it
   leads to higher quality at the same available bit-rate.  To achieve
   this, a Long-Term Prediction (LTP) analysis is carried out to
   estimate the coefficients of a fifth order LTP filter for each of
   four sub-frames.  The LTP coefficients are used to find an LTP
   residual signal with the simulated output signal as input to obtain
   better modelling of the output signal.  This LTP residual signal is
   the input to an LPC analysis where the LPCs are estimated using Burgs
   method, such that the residual energy is minimized.  The estimated
   LPCs are converted to a Line Spectral Frequency (LSF) vector, and
   quantized as described in Section 4.2.7.  After quantization, the
   quantized LSF vector is converted to LPC coefficients and hence by
   using these quantized coefficients the encoder remains fully
   synchronized with the decoder.  The LTP coefficients are quantized
   using a method described in Section 4.2.8.  The quantized LPC and LTP
   coefficients are now used to filter the high-pass filtered input
   signal and measure a residual energy for each of the four subframes.

4.2.6.2.  Unvoiced Speech

   For a speech signal that has been classified as unvoiced there is no
   need for LTP filtering as it has already been determined that the
   pre-whitened input signal is not periodic enough within the allowed
   pitch period range for an LTP analysis to be worth-while the cost in
   terms of complexity and rate.  Therefore, the pre-whitened input
   signal is discarded and instead the high-pass filtered input signal
   is used for LPC analysis using Burgs method.  The resulting LPC
   coefficients are converted to an LSF vector, quantized as described
   in the following section and transformed back to obtain quantized LPC
   coefficients.  The quantized LPC coefficients are used to filter the
   high-pass filtered input signal and measure a residual energy for
   each of the four subframes.

4.2.7.  LSF Quantization

   The purpose of quantization in general is to significantly lower the
   bit rate at the cost of some introduced distortion.  A higher rate



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   should always result in lower distortion, and lowering the rate will
   generally lead to higher distortion.  A commonly used but generally
   sub-optimal approach is to use a quantization method with a constant
   rate where only the error is minimized when quantizing.

4.2.7.1.  Rate-Distortion Optimization

   Instead, we minimize an objective function that consists of a
   weighted sum of rate and distortion, and use a codebook with an
   associated non-uniform rate table.  Thus, we take into account that
   the probability mass function for selecting the codebook entries are
   by no means guaranteed to be uniform in our scenario.  The advantage
   of this approach is that it ensures that rarely used codebook vector
   centroids, which are modelling statistical outliers in the training
   set can be quantized with a low error but with a relatively high cost
   in terms of a high rate.  At the same time this approach also
   provides the advantage that frequently used centroids are modelled
   with low error and a relatively low rate.  This approach will lead to
   equal or lower distortion than the fixed rate codebook at any given
   average rate, provided that the data is similar to the data used for
   training the codebook.

4.2.7.2.  Error Mapping

   Instead of minimizing the error in the LSF domain, we map the errors
   to better approximate spectral distortion by applying an individual
   weight to each element in the error vector.  The weight vectors are
   calculated for each input vector using the Inverse Harmonic Mean
   Weighting (IHMW) function proposed by Laroia et al., see
   [laroia-icassp].  Consequently, we solve the following minimization
   problem, i.e.,


         LSF_q = argmin { (LSF - c)' * W * (LSF - c) + mu * rate },
                 c in C


   where LSF_q is the quantized vector, LSF is the input vector to be
   quantized, and c is the quantized LSF vector candidate taken from the
   set C of all possible outcomes of the codebook.

4.2.7.3.  Multi-Stage Vector Codebook

   We arrange the codebook in a multiple stage structure to achieve a
   quantizer that is both memory efficient and highly scalable in terms
   of computational complexity, see e.g. [sinervo-norsig].  In the first
   stage the input is the LSF vector to be quantized, and in any other
   stage s > 1, the input is the quantization error from the previous



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   stage, see Figure 4.


         Stage 1:           Stage 2:                Stage S:
       +----------+       +----------+            +----------+
       |  c_{1,1} |       |  c_{2,1} |            |  c_{S,1} |
   LSF +----------+ res_1 +----------+  res_{S-1} +----------+
   --->|  c_{1,2} |------>|  c_{2,2} |--> ... --->|  c_{S,2} |--->
       +----------+       +----------+            +----------+ res_S =
           ...                ...                     ...      LSF-LSF_q
       +----------+       +----------+            +----------+
       |c_{1,M1-1}|       |c_{2,M2-1}|            |c_{S,MS-1}|
       +----------+       +----------+            +----------+
       | c_{1,M1} |       | c_{2,M2} |            | c_{S,MS} |
       +----------+       +----------+            +----------+


                Multi-Stage LSF Vector Codebook Structure.

                                 Figure 4

   By storing total of M codebook vectors, i.e.,


                                      S
                                     __
                                 M = \  Ms,
                                     /_
                                     s=1


   where M_s is the number of vectors in stage s, we obtain a total of


                                      S
                                     ___
                                 T = | | Ms
                                     s=1


   possible combinations for generating the quantized vector.  It is for
   example possible to represent 2^36 uniquely combined vectors using
   only 216 vectors in memory, as done in SILK for voiced speech at all
   sample frequencies above 8 kHz.







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4.2.7.4.  Survivor Based Codebook Search

   This number of possible combinations is far too high for a full
   search to be carried out for each frame so for all stages but the
   last, i.e., s smaller than S, only the best min( L, Ms ) centroids
   are carried over to stage s+1.  In each stage the objective function,
   i.e., the weighted sum of accumulated bit-rate and distortion, is
   evaluated for each codebook vector entry and the results are sorted.
   Only the best paths and the corresponding quantization errors are
   considered in the next stage.  In the last stage S the single best
   path through the multistage codebook is determined.  By varying the
   maximum number of survivors from each stage to the next L, the
   complexity can be adjusted in real-time at the cost of a potential
   increase when evaluating the objective function for the resulting
   quantized vector.  This approach scales all the way between the two
   extremes, L=1 being a greedy search, and the desirable but infeasible
   full search, L=T/MS.  In fact, a performance almost as good as what
   can be achieved with the infeasible full search can be obtained at a
   substantially lower complexity by using this approach, see e.g.
   [leblanc-tsap].

4.2.7.5.  LSF Stabilization

   If the input is stable, finding the best candidate will usually
   result in the quantized vector also being stable, but due to the
   multi-stage approach it could in theory happen that the best
   quantization candidate is unstable and because of this there is a
   need to explicitly ensure that the quantized vectors are stable.
   Therefore we apply a LSF stabilization method which ensures that the
   LSF parameters are within valid range, increasingly sorted, and have
   minimum distances between each other and the border values that have
   been pre-determined as the 0.01 percentile distance values from a
   large training set.

4.2.7.6.  Off-Line Codebook Training

   The vectors and rate tables for the multi-stage codebook have been
   trained by minimizing the average of the objective function for LSF
   vectors from a large training set.

4.2.8.  LTP Quantization

   For voiced frames, the prediction analysis described in
   Section 4.2.6.1 resulted in four sets (one set per subframe) of five
   LTP coefficients, plus four weighting matrices.  Also, the LTP
   coefficients for each subframe are quantized using entropy
   constrained vector quantization.  A total of three vector codebooks
   are available for quantization, with different rate-distortion trade-



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   offs.  The three codebooks have 10, 20 and 40 vectors and average
   rates of about 3, 4, and 5 bits per vector, respectively.
   Consequently, the first codebook has larger average quantization
   distortion at a lower rate, whereas the last codebook has smaller
   average quantization distortion at a higher rate.  Given the
   weighting matrix W_ltp and LTP vector b, the weighted rate-distortion
   measure for a codebook vector cb_i with rate r_i is give by


               RD = u * (b - cb_i)' * W_ltp * (b - cb_i) + r_i,


   where u is a fixed, heuristically-determined parameter balancing the
   distortion and rate.  Which codebook gives the best performance for a
   given LTP vector depends on the weighting matrix for that LTP vector.
   For example, for a low valued W_ltp, it is advantageous to use the
   codebook with 10 vectors as it has a lower average rate.  For a large
   W_ltp, on the other hand, it is often better to use the codebook with
   40 vectors, as it is more likely to contain the best codebook vector.
   The weighting matrix W_ltp depends mostly on two aspects of the input
   signal.  The first is the periodicity of the signal; the more
   periodic the larger W_ltp.  The second is the change in signal energy
   in the current subframe, relative to the signal one pitch lag
   earlier.  A decaying energy leads to a larger W_ltp than an
   increasing energy.  Both aspects do not fluctuate very fast which
   causes the W_ltp matrices for different subframes of one frame often
   to be similar.  As a result, one of the three codebooks typically
   gives good performance for all subframes.  Therefore the codebook
   search for the subframe LTP vectors is constrained to only allow
   codebook vectors to be chosen from the same codebook, resulting in a
   rate reduction.

   To find the best codebook, each of the three vector codebooks is used
   to quantize all subframe LTP vectors and produce a combined weighted
   rate-distortion measure for each vector codebook and the vector
   codebook with the lowest combined rate-distortion over all subframes
   is chosen.  The quantized LTP vectors are used in the noise shaping
   quantizer, and the index of the codebook plus the four indices for
   the four subframe codebook vectors are passed on to the range
   encoder.

4.2.9.  Noise Shaping Quantizer

   The noise shaping quantizer independently shapes the signal and
   coding noise spectra to obtain a perceptually higher quality at the
   same bitrate.

   The prefilter output signal is multiplied with a compensation gain G



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   computed in the noise shaping analysis.  Then the output of a
   synthesis shaping filter is added, and the output of a prediction
   filter is subtracted to create a residual signal.  The residual
   signal is multiplied by the inverse quantized quantization gain from
   the noise shaping analysis, and input to a scalar quantizer.  The
   quantization indices of the scalar quantizer represent a signal of
   pulses that is input to the pyramid range encoder.  The scalar
   quantizer also outputs a quantization signal, which is multiplied by
   the quantized quantization gain from the noise shaping analysis to
   create an excitation signal.  The output of the prediction filter is
   added to the excitation signal to form the quantized output signal
   y(n).  The quantized output signal y(n) is input to the synthesis
   shaping and prediction filters.

4.2.10.  Range Encoder

   Range encoding is a well known method for entropy coding in which a
   bitstream sequence is continually updated with every new symbol,
   based on the probability for that symbol.  It is similar to
   arithmetic coding but rather than being restricted to generating
   binary output symbols, it can generate symbols in any chosen number
   base.  In SILK all side information is range encoded.  Each quantized
   parameter has its own cumulative density function based on histograms
   for the quantization indices obtained by running a training database.

4.2.10.1.  Bitstream Encoding Details

   TBD.

4.3.  CELT Encoder

   Copy from CELT draft.

4.3.1.  Forward MDCT

   The MDCT implementation has no special characteristics.  The input is
   a windowed signal (after pre-emphasis) of 2*N samples and the output
   is N frequency-domain samples.  A _low-overlap_ window is used to
   reduce the algorithmic delay.  It is derived from a basic (full
   overlap) window that is the same as the one used in the Vorbis codec:
   W(n)=[sin(pi/2*sin(pi/2*(n+.5)/L))]^2.  The low-overlap window is
   created by zero-padding the basic window and inserting ones in the
   middle, such that the resulting window still satisfies power
   complementarity.  The MDCT is computed in mdct_forward() (mdct.c),
   which includes the windowing operation and a scaling of 2/N.






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4.3.2.  Bands and Normalization

   The MDCT output is divided into bands that are designed to match the
   ear's critical bands, with the exception that each band has to be at
   least 3 bins wide.  For each band, the encoder computes the energy
   that will later be encoded.  Each band is then normalized by the
   square root of the *non-quantized* energy, such that each band now
   forms a unit vector X. The energy and the normalization are computed
   by compute_band_energies() and normalise_bands() (bands.c),
   respectively.

4.3.3.  Energy Envelope Quantization

   It is important to quantize the energy with sufficient resolution
   because any energy quantization error cannot be compensated for at a
   later stage.  Regardless of the resolution used for encoding the
   shape of a band, it is perceptually important to preserve the energy
   in each band.  CELT uses a coarse-fine strategy for encoding the
   energy in the base-2 log domain, as implemented in quant_bands.c

4.3.3.1.  Coarse energy quantization

   The coarse quantization of the energy uses a fixed resolution of 6 dB
   and is the only place where entropy coding is used.  To minimize the
   bitrate, prediction is applied both in time (using the previous
   frame) and in frequency (using the previous bands).  The 2-D
   z-transform of the prediction filter is: A(z_l, z_b)=(1-a*z_l^-1)*(1-
   z_b^-1)/(1-b*z_b^-1) where b is the band index and l is the frame
   index.  The prediction coefficients are a=0.8 and b=0.7 when not
   using intra energy and a=b=0 when using intra energy.  The time-
   domain prediction is based on the final fine quantization of the
   previous frame, while the frequency domain (within the current frame)
   prediction is based on coarse quantization only (because the fine
   quantization has not been computed yet).  We approximate the ideal
   probability distribution of the prediction error using a Laplace
   distribution.  The coarse energy quantization is performed by
   quant_coarse_energy() and quant_coarse_energy() (quant_bands.c).

   The Laplace distribution for each band is defined by a 16-bit (Q15)
   decay parameter.  Thus, the value 0 has a frequency count of
   p[0]=2*(16384*(16384-decay)/(16384+decay)).  The values +/- i each
   have a frequency count p[i] = (p[i-1]*decay)>>14.  The value of p[i]
   is always rounded down (to avoid exceeding 32768 as the sum of all
   frequency counts), so it is possible for the sum to be less than
   32768.  In that case additional values with a frequency count of 1
   are encoded.  The signed values corresponding to symbols 0, 1, 2, 3,
   4, ... are [0, +1, -1, +2, -2, ...].  The encoding of the Laplace-
   distributed values is implemented in ec_laplace_encode() (laplace.c).



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4.3.3.2.  Fine energy quantization

   After the coarse energy quantization and encoding, the bit allocation
   is computed (Section 4.3.4) and the number of bits to use for
   refining the energy quantization is determined for each band.  Let
   B_i be the number of fine energy bits for band i; the refinement is
   an integer f in the range [0,2^B_i-1].  The mapping between f and the
   correction applied to the coarse energy is equal to (f+1/2)/2^B_i -
   1/2.  Fine energy quantization is implemented in quant_fine_energy()
   (quant_bands.c).

   If any bits are unused at the end of the encoding process, these bits
   are used to increase the resolution of the fine energy encoding in
   some bands.  Priority is given to the bands for which the allocation
   (Section 4.3.4) was rounded down.  At the same level of priority,
   lower bands are encoded first.  Refinement bits are added until there
   are no unused bits.  This is implemented in quant_energy_finalise()
   (quant_bands.c).

4.3.4.  Bit Allocation

   Bit allocation is performed based only on information available to
   both the encoder and decoder.  The same calculations are performed in
   a bit-exact manner in both the encoder and decoder to ensure that the
   result is always exactly the same.  Any mismatch would cause an error
   in the decoded output.  The allocation is computed by
   compute_allocation() (rate.c), which is used in both the encoder and
   the decoder.

   For a given band, the bit allocation is nearly constant across frames
   that use the same number of bits for Q1, yielding a pre-defined
   signal-to-mask ratio (SMR) for each band.  Because the bands each
   have a width of one Bark, this is equivalent to modeling the masking
   occurring within each critical band, while ignoring inter-band
   masking and tone-vs-noise characteristics.  While this is not an
   optimal bit allocation, it provides good results without requiring
   the transmission of any allocation information.

   For every encoded or decoded frame, a target allocation must be
   computed using the projected allocation.  In the reference
   implementation this is performed by compute_allocation() (rate.c).
   The target computation begins by calculating the available space as
   the number of whole bits which can be fit in the frame after Q1 is
   stored according to the range coder (ec_[enc/dec]_tell()) and then
   multiplying by 8.  Then the two projected prototype allocations whose
   sums multiplied by 8 are nearest to that value are determined.  These
   two projected prototype allocations are then interpolated by finding
   the highest integer interpolation coefficient in the range 0-8 such



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   that the sum of the higher prototype times the coefficient, plus the
   sum of the lower prototype multiplied by the difference of 16 and the
   coefficient, is less than or equal to the available sixteenth-bits.
   The reference implementation performs this step using a binary search
   in interp_bits2pulses() (rate.c).  The target allocation is the
   interpolation coefficient times the higher prototype, plus the lower
   prototype multiplied by the difference of 16 and the coefficient, for
   each of the CELT bands.

   Because the computed target will sometimes be somewhat smaller than
   the available space, the excess space is divided by the number of
   bands, and this amount is added equally to each band.  Any remaining
   space is added to the target one sixteenth-bit at a time, starting
   from the first band.  The new target now matches the available space,
   in sixteenth-bits, exactly.

   The allocation target is separated into a portion used for fine
   energy and a portion used for the Spherical Vector Quantizer (PVQ).
   The fine energy quantizer operates in whole-bit steps.  For each band
   the number of bits per channel used for fine energy is calculated by
   50 minus the log2_frac(), with 1/16 bit precision, of the number of
   MDCT bins in the band.  That result is multiplied by the number of
   bins in the band and again by twice the number of channels, and then
   the value is set to zero if it is less than zero.  Added to that
   result is 16 times the number of MDCT bins times the number of
   channels, and it is finally divided by 32 times the number of MDCT
   bins times the number of channels.  If the result times the number of
   channels is greater than than the target divided by 16, the result is
   set to the target divided by the number of channels divided by 16.
   Then if the value is greater than 7 it is reset to 7 because a larger
   amount of fine energy resolution was determined not to be make an
   improvement in perceived quality.  The resulting number of fine
   energy bits per channel is then multiplied by the number of channels
   and then by 16, and subtracted from the target allocation.  This
   final target allocation is what is used for the PVQ.

4.3.5.  Pitch Prediction

   This section needs to be updated.

4.3.6.  Spherical Vector Quantization

   CELT uses a Pyramid Vector Quantization (PVQ) [PVQ] codebook for
   quantizing the details of the spectrum in each band that have not
   been predicted by the pitch predictor.  The PVQ codebook consists of
   all sums of K signed pulses in a vector of N samples, where two
   pulses at the same position are required to have the same sign.  Thus
   the codebook includes all integer codevectors y of N dimensions that



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   satisfy sum(abs(y(j))) = K.

   In bands where neither pitch nor folding is used, the PVQ is used to
   encode the unit vector that results from the normalization in
   Section 4.3.2 directly.  Given a PVQ codevector y, the unit vector X
   is obtained as X = y/||y||, where ||.|| denotes the L2 norm.

4.3.6.1.  Bits to Pulses

   Although the allocation is performed in 1/16 bit units, the
   quantization requires an integer number of pulses K. To do this, the
   encoder searches for the value of K that produces the number of bits
   that is the nearest to the allocated value (rounding down if exactly
   half-way between two values), subject to not exceeding the total
   number of bits available.  The computation is performed in 1/16 of
   bits using log2_frac() and ec_enc_tell().  The number of codebooks
   entries can be computed as explained in Section 4.3.6.3.  The
   difference between the number of bits allocated and the number of
   bits used is accumulated to a _balance_ (initialised to zero) that
   helps adjusting the allocation for the next bands.  One third of the
   balance is subtracted from the bit allocation of the next band to
   help achieving the target allocation.  The only exceptions are the
   band before the last and the last band, for which half the balance
   and the whole balance are subtracted, respectively.

4.3.6.2.  PVQ Search

   The search for the best codevector y is performed by alg_quant()
   (vq.c).  There are several possible approaches to the search with a
   tradeoff between quality and complexity.  The method used in the
   reference implementation computes an initial codeword y1 by
   projecting the residual signal R = X - p' onto the codebook pyramid
   of K-1 pulses:

   y0 = round_towards_zero( (K-1) * R / sum(abs(R)))

   Depending on N, K and the input data, the initial codeword y0 may
   contain from 0 to K-1 non-zero values.  All the remaining pulses,
   with the exception of the last one, are found iteratively with a
   greedy search that minimizes the normalized correlation between y and
   R:

   J = -R^T*y / ||y||

   The search described above is considered to be a good trade-off
   between quality and computational cost.  However, there are other
   possible ways to search the PVQ codebook and the implementors MAY use
   any other search methods.



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4.3.6.3.  Index Encoding

   The best PVQ codeword is encoded as a uniformly-distributed integer
   value by encode_pulses() (cwrs.c).  The codeword is converted to a
   unique index in the same way as specified in [PVQ].  The indexing is
   based on the calculation of V(N,K) (denoted N(L,K) in [PVQ]), which
   is the number of possible combinations of K pulses in N samples.  The
   number of combinations can be computed recursively as V(N,K) =
   V(N+1,K) + V(N,K+1) + V(N+1,K+1), with V(N,0) = 1 and V(0,K) = 0, K
   != 0.  There are many different ways to compute V(N,K), including
   pre-computed tables and direct use of the recursive formulation.  The
   reference implementation applies the recursive formulation one line
   (or column) at a time to save on memory use, along with an alternate,
   univariate recurrence to initialise an arbitrary line, and direct
   polynomial solutions for small N. All of these methods are
   equivalent, and have different trade-offs in speed, memory usage, and
   code size.  Implementations MAY use any methods they like, as long as
   they are equivalent to the mathematical definition.

   The indexing computations are performed using 32-bit unsigned
   integers.  For large codebooks, 32-bit integers are not sufficient.
   Instead of using 64-bit integers (or more), the encoding is made
   slightly sub-optimal by splitting each band into two equal (or near-
   equal) vectors of size (N+1)/2 and N/2, respectively.  The number of
   pulses in the first half, K1, is first encoded as an integer in the
   range [0,K].  Then, two codebooks are encoded with V((N+1)/2, K1) and
   V(N/2, K-K1).  The split operation is performed recursively, in case
   one (or both) of the split vectors still requires more than 32 bits.
   For compatibility reasons, the handling of codebooks of more than 32
   bits MUST be implemented with the splitting method, even if 64-bit
   arithmetic is available.

4.3.7.  Stereo support

   When encoding a stereo stream, some parameters are shared across the
   left and right channels, while others are transmitted separately for
   each channel, or jointly encoded.  Only one copy of the flags for the
   features, transients and pitch (pitch period and gains) are
   transmitted.  The coarse and fine energy parameters are transmitted
   separately for each channel.  Both the coarse energy and fine energy
   (including the remaining fine bits at the end of the stream) have the
   left and right bands interleaved in the stream, with the left band
   encoded first.

   The main difference between mono and stereo coding is the PVQ coding
   of the normalized vectors.  In stereo mode, a normalized mid-side
   (M-S) encoding is used.  Let L and R be the normalized vector of a
   certain band for the left and right channels, respectively.  The mid



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   and side vectors are computed as M=L+R and S=L-R and no longer have
   unit norm.

   From M and S, an angular parameter theta=2/pi*atan2(||S||, ||M||) is
   computed.  The theta parameter is converted to a Q14 fixed-point
   parameter itheta, which is quantized on a scale from 0 to 1 with an
   interval of 2^-qb, where qb = (b-2*(N-1)*(40-log2_frac(N,4)))/
   (32*(N-1)), b is the number of bits allocated to the band, and
   log2_frac() is defined in cwrs.c.  From here on, the value of itheta
   MUST be treated in a bit-exact manner since both the encoder and
   decoder rely on it to infer the bit allocation.

   Let m=M/||M|| and s=S/||S||; m and s are separately encoded with the
   PVQ encoder described in Section 4.3.6.  The number of bits allocated
   to m and s depends on the value of itheta.  The number of bits
   allocated to coding m is obtained by:

      imid = bitexact_cos(itheta);

      iside = bitexact_cos(16384-itheta);

      delta = (N-1)*(log2_frac(iside,6)-log2_frac(imid,6))>>2;

      qalloc = log2_frac((1<<qb)+1,4);

      mbits = (b-qalloc/2-delta)/2;

   where bitexact_cos() is a fixed-point cosine approximation that MUST
   be bit-exact with the reference implementation in mathops.h.  The
   spectral folding operation is performed independently for the mid and
   side vectors.

4.3.8.  Synthesis

   After all the quantization is completed, the quantized energy is used
   along with the quantized normalized band data to resynthesize the
   MDCT spectrum.  The inverse MDCT (Section 5.3.5) and the weighted
   overlap-add are applied and the signal is stored in the _synthesis
   buffer_ so it can be used for pitch prediction.  The encoder MAY omit
   this step of the processing if it knows that it will not be using the
   pitch predictor for the next few frames.  If the de-emphasis filter
   (Section 5.3.5) is applied to this resynthesized signal, then the
   output will be the same (within numerical precision) as the decoder's
   output.







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4.3.9.  Variable Bitrate (VBR)

   Each CELT frame can be encoded in a different number of octets,
   making it possible to vary the bitrate at will.  This property can be
   used to implement source-controlled variable bitrate (VBR).  Support
   for VBR is OPTIONAL for the encoder, but a decoder MUST be prepared
   to decode a stream that changes its bit-rate dynamically.  The method
   used to vary the bit-rate in VBR mode is left to the implementor, as
   long as each frame can be decoded by the reference decoder.










































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5.  Codec Decoder

   Opus decoder block diagram.

5.1.  Range Decoder

   The range decoder extracts the symbols and integers encoded using the
   range encoder in Section 4.1.  The range decoder maintains an
   internal state vector composed of the two-tuple (dif,rng),
   representing the difference between the high end of the current range
   and the actual coded value, and the size of the current range,
   respectively.  Both dif and rng are 32-bit unsigned integer values.
   rng is initialized to 2^7. dif is initialized to rng minus the top 7
   bits of the first input octet.  Then the range is immediately
   normalized, using the procedure described in the following section.

5.1.1.  Decoding Symbols

   Decoding symbols is a two-step process.  The first step determines a
   value fs that lies within the range of some symbol in the current
   context.  The second step updates the range decoder state with the
   three-tuple (fl,fh,ft) corresponding to that symbol, as defined in
   Section 4.1.1.

   The first step is implemented by ec_decode() (rangedec.c), and
   computes fs = ft-min((dif-1)/(rng/ft)+1,ft), where ft is the sum of
   the frequency counts in the current context, as described in
   Section 4.1.1.  The divisions here are exact integer division.

   In the reference implementation, a special version of ec_decode()
   called ec_decode_bin() (rangeenc.c) is defined using the parameter
   ftb instead of ft.  It is mathematically equivalent to calling
   ec_decode() with ft = (1<<ftb), but avoids one of the divisions.

   The decoder then identifies the symbol in the current context
   corresponding to fs; i.e., the one whose three-tuple (fl,fh,ft)
   satisfies fl <= fs < fh.  This tuple is used to update the decoder
   state according to dif = dif - (rng/ft)*(ft-fh), and if fl is greater
   than zero, rng = (rng/ft)*(fh-fl), or otherwise rng = rng - (rng/
   ft)*(ft-fh).  After this update, the range is normalized.

   To normalize the range, the following process is repeated until rng >
   2^23.  First, rng is set to (rng<8)&0xFFFFFFFF.  Then the next 8 bits
   of input are read into sym, using the remaining bit from the previous
   input octet as the high bit of sym, and the top 7 bits of the next
   octet for the remaining bits of sym.  If no more input octets remain,
   zero bits are used instead.  Then, dif is set to (dif<<8)-sym&
   0xFFFFFFFF (i.e., using wrap-around if the subtraction overflows a



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   32-bit register).  Finally, if dif is larger than 2^31, dif is then
   set to dif - 2^31.  This process is carried out by ec_dec_normalize()
   (rangedec.c).

5.1.2.  Decoding Uniformly Distributed Integers

   Functions ec_dec_uint() or ec_dec_bits() are based on ec_decode() and
   decode one of N equiprobable symbols, each with a frequency of 1,
   where N may be as large as 2^32-1.  Because ec_decode() is limited to
   a total frequency of 2^16-1, this is done by decoding a series of
   symbols in smaller contexts.

   ec_dec_bits() (entdec.c) is defined, like ec_decode_bin(), to take a
   single parameter ftb, with ftb < 32. and ftb < 32, and produces an
   ftb-bit decoded integer value, t, initialized to zero.  While ftb is
   greater than 8, it decodes the next 8 most significant bits of the
   integer, s = ec_decode_bin(8), updates the decoder state with the
   3-tuple (s,s+1,256), adds those bits to the current value of t, t =
   t<<8 | s, and subtracts 8 from ftb.  Then it decodes the remaining
   bits of the integer, s = ec_decode_bin(ftb), updates the decoder
   state with the 3 tuple (s,s+1,1<<ftb), and adds those bits to the
   final values of t, t = t<<ftb | s.

   ec_dec_uint() (entdec.c) takes a single parameter, ft, which is not
   necessarily a power of two, and returns an integer, t, with a value
   between 0 and ft-1, inclusive, which is initialized to zero.  Let ftb
   be the location of the highest 1 bit in the two's-complement
   representation of (ft-1), or -1 if no bits are set.  If ftb>8, then
   the top 8 bits of t are decoded using t = ec_decode((ft-1>>ftb-8)+1),
   the decoder state is updated with the three-tuple (s,s+
   1,(ft-1>>ftb-8)+1), and the remaining bits are decoded with t =
   t<<ftb-8|ec_dec_bits(ftb-8).  If, at this point, t >= ft, then the
   current frame is corrupt, and decoding should stop.  If the original
   value of ftb was not greater than 8, then t is decoded with t =
   ec_decode(ft), and the decoder state is updated with the three-tuple
   (t,t+1,ft).

5.1.3.  Current Bit Usage

   The bit allocation routines in CELT need to be able to determine a
   conservative upper bound on the number of bits that have been used to
   decode from the current frame thus far.  This drives allocation
   decisions which must match those made in the encoder.  This is
   computed in the reference implementation to fractional bit precision
   by the function ec_dec_tell() (rangedec.c).  Like all operations in
   the range decoder, it must be implemented in a bit-exact manner, and
   must produce exactly the same value returned by ec_enc_tell() after
   encoding the same symbols.



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5.2.  SILK Decoder

   At the receiving end, the received packets are by the range decoder
   split into a number of frames contained in the packet.  Each of which
   contains the necessary information to reconstruct a 20 ms frame of
   the output signal.

5.2.1.  Decoder Modules

   An overview of the decoder is given in Figure 5.



      +---------+    +------------+
   -->| Range   |--->| Decode     |---------------------------+
    1 | Decoder | 2  | Parameters |----------+       5        |
      +---------+    +------------+     4    |                |
                          3 |                |                |
                           \/               \/               \/
                     +------------+   +------------+   +------------+
                     | Generate   |-->| LTP        |-->| LPC        |-->
                     | Excitation |   | Synthesis  |   | Synthesis  | 6
                     +------------+   +------------+   +------------+

   1: Range encoded bitstream
   2: Coded parameters
   3: Pulses and gains
   4: Pitch lags and LTP coefficients
   5: LPC coefficients
   6: Decoded signal


                          Decoder block diagram.

                                 Figure 5

5.2.1.1.  Range Decoder

   The range decoder decodes the encoded parameters from the received
   bitstream.  Output from this function includes the pulses and gains
   for the excitation signal generation, as well as LTP and LSF codebook
   indices, which are needed for decoding LTP and LPC coefficients
   needed for LTP and LPC synthesis filtering the excitation signal,
   respectively.







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5.2.1.2.  Decode Parameters

   Pulses and gains are decoded from the parameters that was decoded by
   the range decoder.

   When a voiced frame is decoded and LTP codebook selection and indices
   are received, LTP coefficients are decoded using the selected
   codebook by choosing the vector that corresponds to the given
   codebook index in that codebook.  This is done for each of the four
   subframes.  The LPC coefficients are decoded from the LSF codebook by
   first adding the chosen vectors, one vector from each stage of the
   codebook.  The resulting LSF vector is stabilized using the same
   method that was used in the encoder, see Section 4.2.7.5.  The LSF
   coefficients are then converted to LPC coefficients, and passed on to
   the LPC synthesis filter.

5.2.1.3.  Generate Excitation

   The pulses signal is multiplied with the quantization gain to create
   the excitation signal.

5.2.1.4.  LTP Synthesis

   For voiced speech, the excitation signal e(n) is input to an LTP
   synthesis filter that will recreate the long term correlation that
   was removed in the LTP analysis filter and generate an LPC excitation
   signal e_LPC(n), according to


                                     d
                                    __
                  e_LPC(n) = e(n) + \  e(n - L - i) * b_i,
                                    /_
                                   i=-d


   using the pitch lag L, and the decoded LTP coefficients b_i.  For
   unvoiced speech, the output signal is simply a copy of the excitation
   signal, i.e., e_LPC(n) = e(n).

5.2.1.5.  LPC Synthesis

   In a similar manner, the short-term correlation that was removed in
   the LPC analysis filter is recreated in the LPC synthesis filter.
   The LPC excitation signal e_LPC(n) is filtered using the LTP
   coefficients a_i, according to





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                                   d_LPC
                                    __
                  y(n) = e_LPC(n) + \  e_LPC(n - i) * a_i,
                                    /_
                                    i=1


   where d_LPC is the LPC synthesis filter order, and y(n) is the
   decoded output signal.

5.3.  CELT Decoder

   Insert decoder figure.

   The decoder extracts information from the range-coded bit-stream in
   the same order as it was encoded by the encoder.  In some
   circumstances, it is possible for a decoded value to be out of range
   due to a very small amount of redundancy in the encoding of large
   integers by the range coder.  In that case, the decoder should assume
   there has been an error in the coding, decoding, or transmission and
   SHOULD take measures to conceal the error and/or report to the
   application that a problem has occurred.

5.3.1.  Energy Envelope Decoding

   The energy of each band is extracted from the bit-stream in two steps
   according to the same coarse-fine strategy used in the encoder.
   First, the coarse energy is decoded in unquant_coarse_energy()
   (quant_bands.c) based on the probability of the Laplace model used by
   the encoder.

   After the coarse energy is decoded, the same allocation function as
   used in the encoder is called.  This determines the number of bits to
   decode for the fine energy quantization.  The decoding of the fine
   energy bits is performed by unquant_fine_energy() (quant_bands.c).
   Finally, like the encoder, the remaining bits in the stream (that
   would otherwise go unused) are decoded using
   unquant_energy_finalise() (quant_bands.c).

5.3.2.  Pitch prediction decoding

   If the pitch bit is set, then the pitch period is extracted from the
   bit-stream.  The pitch gain bits are extracted within the PVQ
   decoding as encoded by the encoder.  When the folding bit is set, the
   folding prediction is computed in exactly the same way as the
   encoder, with the same gain, by the function intra_fold() (vq.c).





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5.3.3.  Spherical VQ Decoder

   In order to correctly decode the PVQ codewords, the decoder must
   perform exactly the same bits to pulses conversion as the encoder.

5.3.3.1.  Index Decoding

   The decoding of the codeword from the index is performed as specified
   in [PVQ], as implemented in function decode_pulses() (cwrs.c).

5.3.3.2.  Normalised Vector Decoding

   The spherical codebook is decoded by alg_unquant() (vq.c).  The index
   of the PVQ entry is obtained from the range coder and converted to a
   pulse vector by decode_pulses() (cwrs.c).

   The decoded normalized vector for each band is equal to

   X' = y/||y||,

   This operation is implemented in mix_pitch_and_residual() (vq.c),
   which is the same function as used in the encoder.

5.3.4.  Denormalization

   Just like each band was normalized in the encoder, the last step of
   the decoder before the inverse MDCT is to denormalize the bands.
   Each decoded normalized band is multiplied by the square root of the
   decoded energy.  This is done by denormalise_bands() (bands.c).

5.3.5.  Inverse MDCT

   The inverse MDCT implementation has no special characteristics.  The
   input is N frequency-domain samples and the output is 2*N time-domain
   samples, while scaling by 1/2.  The output is windowed using the same
   window as the encoder.  The IMDCT and windowing are performed by
   mdct_backward (mdct.c).  If a time-domain pre-emphasis window was
   applied in the encoder, the (inverse) time-domain de-emphasis window
   is applied on the IMDCT result.  After the overlap-add process, the
   signal is de-emphasized using the inverse of the pre-emphasis filter
   used in the encoder: 1/A(z)=1/(1-alpha_p*z^-1).

5.3.6.  Packet Loss Concealment (PLC)

   Packet loss concealment (PLC) is an optional decoder-side feature
   which SHOULD be included when transmitting over an unreliable
   channel.  Because PLC is not part of the bit-stream, there are
   several possible ways to implement PLC with different complexity/



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   quality trade-offs.  The PLC in the reference implementation finds a
   periodicity in the decoded signal and repeats the windowed waveform
   using the pitch offset.  The windowed waveform is overlapped in such
   a way as to preserve the time-domain aliasing cancellation with the
   previous frame and the next frame.  This is implemented in
   celt_decode_lost() (mdct.c).













































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6.  Security Considerations

   The codec needs to take appropriate security considerations into
   account, as outlined in [DOS] and [SECGUIDE].  It is extremely
   important for the decoder to be robust against malicious payloads.
   Malicious payloads must not cause the decoder to overrun its
   allocated memory or to take much more resources to decode.  Although
   problems in encoders are typically rarer, the same applies to the
   encoder.  Malicious audio stream must not cause the encoder to
   misbehave because this would allow an attacker to attack transcoding
   gateways.

   In its current version, the Opus codec likely does NOT meet these
   security considerations, so it should be used with caution.





































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7.  IANA Considerations

   This document has no actions for IANA.
















































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8.  Acknowledgments

   Thanks to all other developers, including Raymond Chen, Soeren Skak
   Jensen, Gregory Maxwell, Christopher Montgomery, Karsten Vandborg
   Soerensen, and Timothy Terriberry.














































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9.  Informative References

   [SILK]     Vos, K., Jensen, S., and K. Soerensen, "SILK Speech
              Codec", draft-vos-silk-01 (work in progress), March 2010.

   [laroia-icassp]
              Laroia, R., Phamdo, N., and N. Farvardin, "Robust and
              Efficient Quantization of Speech LSP Parameters Using
              Structured Vector Quantization", ICASSP-1991, Proc. IEEE
              Int. Conf. Acoust., Speech, Signal Processing, pp. 641-
              644, October 1991.

   [sinervo-norsig]
              Sinervo, U., Nurminen, J., Heikkinen, A., and J. Saarinen,
              "Evaluation of Split and Multistage Techniques in LSF
              Quantization", NORSIG-2001, Norsk symposium i
              signalbehandling, Trondheim, Norge, October 2001.

   [leblanc-tsap]
              LeBlanc, W., Bhattacharya, B., Mahmoud, S., and V.
              Cuperman, "Efficient Search and Design Procedures for
              Robust Multi-Stage VQ of LPC Parameters for 4 kb/s Speech
              Coding", IEEE Transactions on Speech and Audio Processing,
              Vol. 1, No. 4, October 1993.

   [CELT]     Valin, J-M., Terriberry, T., Maxwell, G., and C.
              Montgomery, "Constrained-Energy Lapped Transform (CELT)
              Codec", draft-valin-celt-codec-02 (work in progress),
              July 2010.

   [DOS]      Handley, M., Rescorla, E., and IAB, "Internet Denial-of-
              Service Considerations", RFC 4732, December 2006.

   [SECGUIDE]
              Rescorla, E. and B. Korver, "Guidelines for Writing RFC
              Text on Security Considerations", BCP 72, RFC 3552,
              July 2003.

   [range-coding]
              Nigel, G. and N. Martin, "Range encoding: An algorithm for
              removing redundancy from a digitised message", Proc.
              Institution of Electronic and Radio Engineers
              International Conference on Video and Data Recording ,
              1979.

   [coding-thesis]
              Pasco, R., "Source coding algorithms for fast data
              compression", Ph.D. thesis Dept. of Electrical



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              Engineering, Stanford University, May 1976.

   [PVQ]      Fischer, T., "A Pyramid Vector Quantizer", IEEE Trans. on
              Information Theory, Vol. 32 pp. 568-583, July 1986.

   [1]  <http://developer.skype.com/silk>

   [2]  <http://www.celt-codec.org/>

   [3]  <git://git.xiph.org/users/jm/ietfcodec.git>









































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Appendix A.  Reference Implementation

   This appendix contains the complete source code for the reference
   implementation of the Opus codec written in C. This implementation
   can be compiled for either floating-point or fixed-point
   architectures.

   The implementation can be compiled with either a C89 or a C99
   compiler.  It is reasonably optimized for most platforms such that
   only architecture-specific optimizations are likely to be useful.
   The FFT used is a slightly modified version of the KISS-FFT package,
   but it is easy to substitute any other FFT library.

A.1.  Extracting the source

   The complete source code can be extracted from this draft, by running
   the following command line:

   o  cat draft-ietf-codec-opus.txt | grep '^\ \ \ ###' | sed
      's/\s\s\s###//' | base64 -d > opus_source.tar.gz

   o  tar xzvf opus_source.tar.gz

   o  cd opus_source

   o  make

A.2.  Base64-encoded source code

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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 48]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 49]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 50]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 54]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 55]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 56]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 60]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 61]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 62]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 65]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 68]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 71]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 90]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 94]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 95]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 96]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011                [Page 99]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 105]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 119]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 120]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 121]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 124]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 127]


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 139]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 155]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 156]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 157]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 158]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 164]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 166]


Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 167]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 170]


Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Internet-Draft           Interactive Audio Codec           February 2011


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Valin & Vos              Expires August 8, 2011               [Page 183]


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Valin & Vos              Expires August 8, 2011               [Page 184]


Internet-Draft           Interactive Audio Codec           February 2011


Authors' Addresses

   Jean-Marc Valin
   Octasic Inc.
   4101, Molson Street
   Montreal, Quebec
   Canada

   Phone: +1 514 282-8858
   Email: jean-marc.valin@octasic.com


   Koen Vos
   Skype Technologies S.A.
   Stadsgarden 6
   Stockholm,   11645
   SE

   Phone: +46 855 921 989
   Email: koen.vos@skype.net































Valin & Vos              Expires August 8, 2011               [Page 185]


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