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Versions: (draft-ietf-codec-harmony) 00 01 02 03 04 05 06 07 08 09 10 11 12 13 14 15 16 RFC 6716

Network Working Group                                          JM. Valin
Internet-Draft                                              Octasic Inc.
Intended status: Standards Track                                  K. Vos
Expires: September 15, 2011                      Skype Technologies S.A.
                                                          March 14, 2011


                   Definition of the Opus Audio Codec
                        draft-ietf-codec-opus-05

Abstract

   This document describes the Opus codec, designed for interactive
   speech and audio transmission over the Internet.

Status of this Memo

   This Internet-Draft is submitted in full conformance with the
   provisions of BCP 78 and BCP 79.

   Internet-Drafts are working documents of the Internet Engineering
   Task Force (IETF).  Note that other groups may also distribute
   working documents as Internet-Drafts.  The list of current Internet-
   Drafts is at http://datatracker.ietf.org/drafts/current/.

   Internet-Drafts are draft documents valid for a maximum of six months
   and may be updated, replaced, or obsoleted by other documents at any
   time.  It is inappropriate to use Internet-Drafts as reference
   material or to cite them other than as "work in progress."

   This Internet-Draft will expire on September 15, 2011.

Copyright Notice

   Copyright (c) 2011 IETF Trust and the persons identified as the
   document authors.  All rights reserved.

   This document is subject to BCP 78 and the IETF Trust's Legal
   Provisions Relating to IETF Documents
   (http://trustee.ietf.org/license-info) in effect on the date of
   publication of this document.  Please review these documents
   carefully, as they describe your rights and restrictions with respect
   to this document.  Code Components extracted from this document must
   include Simplified BSD License text as described in Section 4.e of
   the Trust Legal Provisions and are provided without warranty as
   described in the Simplified BSD License.





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Table of Contents

   1.  Introduction  . . . . . . . . . . . . . . . . . . . . . . . .   4
   2.  Opus Codec  . . . . . . . . . . . . . . . . . . . . . . . . .   5
     2.1.  Source Code . . . . . . . . . . . . . . . . . . . . . . .   5
   3.  Codec Modes . . . . . . . . . . . . . . . . . . . . . . . . .   6
     3.1.  Examples  . . . . . . . . . . . . . . . . . . . . . . . .   7
   4.  Opus Decoder  . . . . . . . . . . . . . . . . . . . . . . . .   9
     4.1.  Range Decoder . . . . . . . . . . . . . . . . . . . . . .   9
       4.1.1.  Decoding Symbols  . . . . . . . . . . . . . . . . . .  10
       4.1.2.  Alternate Decoding Methods  . . . . . . . . . . . . .  10
       4.1.3.  Decoding Raw Bits . . . . . . . . . . . . . . . . . .  11
       4.1.4.  Decoding Uniformly Distributed Integers . . . . . . .  12
       4.1.5.  Current Bit Usage . . . . . . . . . . . . . . . . . .  12
     4.2.  SILK Decoder  . . . . . . . . . . . . . . . . . . . . . .  12
       4.2.1.  Decoder Modules . . . . . . . . . . . . . . . . . . .  13
     4.3.  CELT Decoder  . . . . . . . . . . . . . . . . . . . . . .  15
       4.3.1.  Transient Decoding  . . . . . . . . . . . . . . . . .  16
       4.3.2.  Energy Envelope Decoding  . . . . . . . . . . . . . .  16
       4.3.3.  Bit allocation  . . . . . . . . . . . . . . . . . . .  17
       4.3.4.  Shape Decoder . . . . . . . . . . . . . . . . . . . .  22
       4.3.5.  Anti-collapse processing  . . . . . . . . . . . . . .  24
       4.3.6.  Denormalization . . . . . . . . . . . . . . . . . . .  24
       4.3.7.  Inverse MDCT  . . . . . . . . . . . . . . . . . . . .  24
       4.3.8.  Packet Loss Concealment (PLC) . . . . . . . . . . . .  25
   5.  Codec Encoder . . . . . . . . . . . . . . . . . . . . . . . .  26
     5.1.  Range Coder . . . . . . . . . . . . . . . . . . . . . . .  26
       5.1.1.  Encoding Symbols  . . . . . . . . . . . . . . . . . .  26
       5.1.2.  Encoding Raw Bits . . . . . . . . . . . . . . . . . .  27
       5.1.3.  Encoding Uniformly Distributed Integers . . . . . . .  28
       5.1.4.  Finalizing the Stream . . . . . . . . . . . . . . . .  28
       5.1.5.  Current Bit Usage . . . . . . . . . . . . . . . . . .  28
     5.2.  SILK Encoder  . . . . . . . . . . . . . . . . . . . . . .  29
       5.2.1.  Voice Activity Detection  . . . . . . . . . . . . . .  30
       5.2.2.  High-Pass Filter  . . . . . . . . . . . . . . . . . .  31
       5.2.3.  Pitch Analysis  . . . . . . . . . . . . . . . . . . .  31
       5.2.4.  Noise Shaping Analysis  . . . . . . . . . . . . . . .  33
       5.2.5.  Prefilter . . . . . . . . . . . . . . . . . . . . . .  37
       5.2.6.  Prediction Analysis . . . . . . . . . . . . . . . . .  37
       5.2.7.  LSF Quantization  . . . . . . . . . . . . . . . . . .  38
       5.2.8.  LTP Quantization  . . . . . . . . . . . . . . . . . .  41
       5.2.9.  Noise Shaping Quantizer . . . . . . . . . . . . . . .  42
       5.2.10. Range Encoder . . . . . . . . . . . . . . . . . . . .  43
     5.3.  CELT Encoder  . . . . . . . . . . . . . . . . . . . . . .  43
       5.3.1.  Pre-filter  . . . . . . . . . . . . . . . . . . . . .  43
       5.3.2.  Forward MDCT  . . . . . . . . . . . . . . . . . . . .  43
       5.3.3.  Bands and Normalization . . . . . . . . . . . . . . .  43
       5.3.4.  Energy Envelope Quantization  . . . . . . . . . . . .  44



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       5.3.5.  Spherical Vector Quantization . . . . . . . . . . . .  45
       5.3.6.  Stereo support  . . . . . . . . . . . . . . . . . . .  46
       5.3.7.  Synthesis . . . . . . . . . . . . . . . . . . . . . .  46
       5.3.8.  Variable Bitrate (VBR)  . . . . . . . . . . . . . . .  47
   6.  Conformance . . . . . . . . . . . . . . . . . . . . . . . . .  48
   7.  Security Considerations . . . . . . . . . . . . . . . . . . .  49
   8.  IANA Considerations . . . . . . . . . . . . . . . . . . . . .  50
   9.  Acknowledgments . . . . . . . . . . . . . . . . . . . . . . .  51
   10. Informative References  . . . . . . . . . . . . . . . . . . .  52
   Appendix A.  Reference Implementation . . . . . . . . . . . . . .  54
     A.1.  Extracting the source . . . . . . . . . . . . . . . . . .  54
     A.2.  Base64-encoded source code  . . . . . . . . . . . . . . .  54
   Appendix B.  opus_compare.m . . . . . . . . . . . . . . . . . . . 197
   Authors' Addresses  . . . . . . . . . . . . . . . . . . . . . . . 199





































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1.  Introduction

   We propose the Opus codec, based on a linear prediction layer (LP)
   and an MDCT-based layer.  The main idea behind the proposal is that
   in speech, low frequencies are usually more efficiently coded using
   linear prediction codecs (such as CELP variants), while music and
   higher speech frequencies are more efficiently coded in the transform
   domain (e.g.  MDCT).  For low sampling rates, the MDCT layer is not
   useful and only the LP-based layer is used.  On the other hand, non-
   speech signals are not always adequately coded using linear
   prediction, so for music only the MDCT-based layer is used.

   The Opus LP layer is based on the SILK [1] codec [SILK] while the
   MDCT layer is based on the CELT [2] codec [CELT].

   The primary normative part of this specification is provided by the
   source code part of the document.  The codec contains significant
   amounts of fixed-point arithmetic which must be performed exactly,
   including all rounding considerations, and so any useful
   specification must make extensive use of domain-specific symbolic
   language to adequately define these operations.  Additionally, any
   conflict between the symbolic representation and the included
   reference implementation must be resolved.  For the practical reasons
   of compatibility and testability it would be advantageous to give the
   reference implementation to have priority in any disagreement.  The C
   language is also one of the most widely understood human-readable
   symbolic representations for machine behavior.  For these reasons
   this RFC utilizes the reference implementation as the sole symbolic
   representation of the codec.

   While the symbolic representation is unambiguous and complete it is
   not always the easiest way to understand the codec's operation.  For
   this reason this document also describes significant parts of the
   codec in English and takes the opportunity to explain the rationale
   behind many of the more surprising elements of the design.  These
   descriptions are intended to be accurate and informative, but the
   limitations of common english sometimes result in ambiguity, so it is
   intended that the reader will always read them alongside the symbolic
   representation.  Numerous references to the implementation are
   provided for this purpose.  The descriptions sometimes differ from
   the reference in ordering or through mathematical simplification
   wherever such deviation made an explanation easier to understand.
   For example, the right shift and left shift operations in the
   reference implementation are often described using division and
   multiplication in the text.  In general, the text is focused on the
   'what' and 'why' while the symbolic representation most clearly
   provides the 'how'.




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2.  Opus Codec

   In hybrid mode, each frame is coded first by the LP layer and then by
   the MDCT layer.  In the current prototype, the cutoff frequency is 8
   kHz.  In the MDCT layer, all bands below 8 kHz are discarded, such
   that there is no coding redundancy between the two layers.  Also,
   both layers use the same instance of the range coder to encode the
   signal, which ensures that no "padding bits" are wasted.  The hybrid
   approach makes it easy to support both constant bit-rate (CBR) and
   varaible bit-rate (VBR) coding.  Although the SILK layer used is VBR,
   it is easy to make the bit allocation of the CELT layer produce a
   final stream that is CBR by using all the bits left unused by the
   SILK layer.

   In addition to their frame size, the SILK and CELT codecs require a
   look-ahead of 5.2 ms and 2.5 ms, respectively.  SILK's look-ahead is
   due to noise shaping estimation (5 ms) and the internal resampling
   (0.2 ms), while CELT's look-ahead is due to the overlapping MDCT
   windows.  To compensate for the difference, the CELT encoder input is
   delayed by 2.7 ms.  This ensures that low frequencies and high
   frequencies arrive at the same time.

2.1.  Source Code

   The source code is currently available in a Git repository [3] which
   references two other repositories (for SILK and CELT).  Development
   snapshots are provided at <http://opus-codec.org/>.
























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3.  Codec Modes

   There are three possible operating modes for the proposed prototype:

   1.  A linear prediction (LP) mode for use in low bit-rate connections
       with up to 8 kHz audio bandwidth (16 kHz sampling rate)

   2.  A hybrid (LP+MDCT) mode for full-bandwidth speech at medium
       bitrates

   3.  An MDCT-only mode for very low delay speech transmission as well
       as music transmission.

   Each of these modes supports a number of different frame sizes and
   sampling rates.  In order to distinguish between the various modes
   and configurations, we define a single-byte table-of-contents (TOC)
   header that can used in the transport layer (e.g., RTP) to signal
   this information.  The following describes the proposed TOC byte.

   The LP mode supports the following configurations (numbered from 0 to
   11):

   o  8 kHz: 10, 20, 40, 60 ms (0..3)

   o  12 kHz: 10, 20, 40, 60 ms (4..7)

   o  16 kHz: 10, 20, 40, 60 ms (8..11)

   for a total of 12 configurations.

   The hybrid mode supports the following configurations (numbered from
   12 to 15):

   o  32 kHz: 10, 20 ms (12..13)

   o  48 kHz: 10, 20 ms (14..15)

   for a total of 4 configurations.

   The MDCT-only mode supports the following configurations (numbered
   from 16 to 31):

   o  8 kHz: 2.5, 5, 10, 20 ms (16..19)

   o  16 kHz: 2.5, 5, 10, 20 ms (20..23)

   o  32 kHz: 2.5, 5, 10, 20 ms (24..27)




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   o  48 kHz: 2.5, 5, 10, 20 ms (28..31)

   for a total of 16 configurations.

   There is thus a total of 32 configurations, encoded in 5 bits.  One
   bit is used to signal mono vs stereo, which leaves 2 bits for the
   number of frames per packets (codes 0 to 3):

   o  0: 1 frame in the packet

   o  1: 2 frames in the packet, each with equal compressed size

   o  2: 2 frames in the packet, with different compressed size

   o  3: arbitrary number of frames in the packet

   For code 2, the TOC byte is followed by the length of the first
   frame, encoded as described below.  For code 3, the TOC byte is
   followed by a byte encoding the number of frames in the packet, with
   the MSB indicating VBR.  In the VBR case, the byte indicating the
   number of frames is followed by N-1 frame lengths encoded as
   described below.  As an additional limit, the audio duration
   contained within a packet MUST NOT exceed 120 ms.

   The compressed size of the frames (if needed) is indicated -- usually
   -- with one byte, with the following meaning:

   o  0: No frame (DTX or lost packet)

   o  1-251: Size of the frame in bytes

   o  252-255: A second byte is needed.  The total size is (size[1]*4)+
      size[0]

   The maximum size representable is 255*4+255=1275 bytes.  For 20 ms
   frames, that represents a bit-rate of 510 kb/s, which is really the
   highest rate anyone would want to use in stereo mode.  Beyond that
   point, lossless codecs would be more appropriate.  It is also roughly
   the maximum useful rate of the MDCT layer, as shortly thereafter
   additional bits are no longer able to improve quality.

3.1.  Examples

   Simplest case: one narrowband mono 20-ms SILK frame







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    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    1    |0|0|0|               compressed data...              |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Two 48 kHz mono 5 ms CELT frames of the same compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    29   |0|0|1|               compressed data...              |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Two 48 kHz mono 20-ms hybrid frames of different compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    15   |0|1|1|       2       |   frame size  |compressed data|
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |                       compressed data...                      |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

   Four 48 kHz stereo 20-ms CELT frame of the same compressed size:


    0                   1                   2                   3
    0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1 2 3 4 5 6 7 8 9 0 1
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+
   |    31   |1|1|0|       4       |      compressed data...       |
   +-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+-+

















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4.  Opus Decoder

   The Opus decoder consists of two main blocks: the SILK decoder and
   the CELT decoder.  The output of the Opus decode is the sum of the
   outputs from the SILK and CELT decoders with proper sample rate
   conversion and delay compensation as illustrated in the block diagram
   below.  At any given time, one or both of the SILK and CELT decoders
   may be active.


                          +-------+    +----------+
                          | SILK  |    |  sample  |
                       +->|encoder|--->|   rate   |----+
   bit-    +-------+   |  |       |    |conversion|    v
   stream  | Range |---+  +-------+    +----------+  /---\  audio
   ------->|decoder|                                 | + |------>
           |       |---+  +-------+    +----------+  \---/
           +-------+   |  | CELT  |    | Delay    |    ^
                       +->|decoder|----| compens- |----+
                          |       |    | ation    |
                          +-------+    +----------+


4.1.  Range Decoder

   Opus uses an entropy coder based upon [range-coding], which is itself
   a rediscovery of the FIFO arithmetic code introduced by
   [coding-thesis].  It is very similar to arithmetic encoding, except
   that encoding is done with digits in any base instead of with bits,
   so it is faster when using larger bases (i.e., an octet).  All of the
   calculations in the range coder must use bit-exact integer
   arithmetic.

   Each symbol is drawn from a finite alphabet and coded in a separate
   _context_ which describes the size of the alphabet and the relative
   frequency of each symbol in that alphabet.  Opus only uses static
   contexts; they are not adapted to the statistics of the data that is
   coded.

   The parameters needed to encode or decode a symbol in a given context
   are represented by a three-tuple (fl,fh,ft), with 0 <= fl < fh <= ft
   <= 65535.  The values of this tuple are derived from the probability
   model for the symbol, represented by traditional _frequency counts_
   (although, since Opus uses static contexts, these are not updated as
   symbols are decoded).  Let f(i) be the frequency of the ith symbol in
   the current context.  Then the three-tuple corresponding to the kth
   symbol is given by fl=sum(f(i),i<k), fh=fl+f(i), and ft=sum(f(i)).




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   The range decoder extracts the symbols and integers encoded using the
   range encoder in Section 5.1.  The range decoder maintains an
   internal state vector composed of the two-tuple (val,rng),
   representing the difference between the high end of the current range
   and the actual coded value, minus one, and the size of the current
   range, respectively.  Both val and rng are 32-bit unsigned integer
   values. rng is initialized to 2^7. val is initialized to rng minus
   the top 7 bits of the first input octet, minus one.  Then the range
   is immediately normalized, using the procedure described in the
   following section.

4.1.1.  Decoding Symbols

   Decoding symbols is a two-step process.  The first step determines a
   value fs, which lies within the range of some symbol in the current
   context.  The second step updates the range decoder state with the
   three-tuple (fl,fh,ft) corresponding to that symbol.

   The first step is implemented by ec_decode() (entdec.c), and computes
   fs = ft-min(val/(rng/ft)+1,ft).  The divisions here are exact integer
   division.

   The decoder then identifies the symbol in the current context
   corresponding to fs; i.e., the one whose three-tuple (fl,fh,ft)
   satisfies fl <= fs < fh.  This tuple is used to update the decoder
   state according to dif = dif - (rng/ft)*(ft-fh), and if fl is greater
   than zero, rng = (rng/ft)*(fh-fl), or otherwise rng = rng - (rng/
   ft)*(ft-fh).  After this update, the range is normalized.

   To normalize the range, the following process is repeated until rng >
   2^23.  First, rng is set to (rng<<8)&0xFFFFFFFF.  Then the next 8
   bits of input are read into sym, using the remaining bit from the
   previous input octet as the high bit of sym, and the top 7 bits of
   the next octet for the remaining bits of sym.  If no more input
   octets remain, zero bits are used instead.  Then, val is set to
   (val<<8)+256-sym-1&0x7FFFFFFF.  If a decoder consumes all of the
   bytes allocated to the current frame, it MUST continue to use zero
   where any further input bytes are required.  This process is carried
   out by ec_dec_normalize() (entdec.c).

4.1.2.  Alternate Decoding Methods

   The reference implementation uses three additional decoding methods
   that are exactly equivalent to the above, but make assumptions and
   simplifications that allow for a much more efficient implementation.

   The first is ec_decode_bin (entdec.c), which is defined using the
   parameter ftb instead of ft.  It is mathematically equivalent to



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   calling ec_decode() with ft = (1<<ftb), but avoids one of the
   divisions.

   The next is ec_dec_bit_logp() (entdec.c), which decodes a single
   binary symbol, replacing both the ec_decode() and ec_dec_update()
   steps.  The context is described by a single parameter, logp, which
   is the (negative of the) base-2 logarithm of the probability of a
   '1'.  It is mathematically equivalent to calling ec_decode() with ft
   = (1<<logp), followed by ec_dec_update() with fl = 0, fh =
   (1<<logp)-1, ft = (1<<logp) if the returned value of fs is less than
   (1<<logp)-1 (a '0' was decoded), and with fl = (1<<logp)-1, fh = ft =
   (1<<logp) otherwise (a '1' was decoded), but it avoids all
   multiplications and divisions.

   The last is ec_dec_icdf() (entdec.c), which decodes a single symbol
   with a table-based context of up to 8 bits, also replacing both the
   ec_decode() and ec_dec_update() steps, as well as the search for the
   decoded symbol inbetween.  The context is described by two
   parameters, an icdf (_inverse_ cumulative distribution function)
   table and ftb.  As with ec_decode_bin(), (1<<ftb) is equivalent to
   ft. idcf[k], on the other hand, stores (1<<ftb)-fh for the kth symbol
   in the context, which is equal to (1<<ftb)-fl for the (k+1)st symbol.
   fl for the 0th symbol is assumed to be 0, and the table is terminated
   by a value of 0 (where fh == ft).  It is mathematically equivalent to
   calling ec_decode() with ft = (1<<ftb), using the returned value fs
   to search the table for the first entry where (1<<ftb)-fs > icdf[k],
   and calling ec_dec_update() with fl = (1<<ftb)-icdf[k-1] (or 0 if k
   == 0), fh = (1<<ftb)-idcf[k], and ft = (1<<ftb).  Combining the
   search with the update allows the division to be replaced by a series
   of multiplications (which are much cheaper), and using an inverse CDF
   allows the representation of frequencies up to 256 in an 8-bit table
   without any special cases.

4.1.3.  Decoding Raw Bits

   The CELT layer also allows directly encoding a series of _raw_ bits,
   outside of the range coder, implemented in ec_dec_bits() (entdec.c).
   This is both more efficient, and more robust to bit-errors, which
   will desynchronize the range coder.  The raw bits are packed at the
   end of the packet, starting by storing the least significant bit of
   the value to be packed in the least significant bit of the last byte,
   filling up to the most significant bit in the last byte, and the
   continuing in the least significant bit of the penultimate byte, and
   so on.  Because the range decoder must read several bytes ahead in
   the stream, the input consumed by raw bits MAY overlap with the input
   consumed by the range coder, and a decoder MUST allow this.  The
   format should render it impossible to attempt to read more raw bits
   than there are actual bits in the frame, though a decoder MAY wish to



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   check for this and report an error.

4.1.4.  Decoding Uniformly Distributed Integers

   The ec_dec_uint() function is based on ec_decode() and decodes one of
   N equiprobable symbols, each with a frequency of 1, where N may be as
   large as 2^32-1.  Because ec_decode() is limited to a total frequency
   of 2^16-1, this is done by decoding a series of symbols in smaller
   contexts.

   ec_dec_uint() (entdec.c) takes a single parameter, ft, which is not
   necessarily a power of two, and returns an integer, t, with a value
   between 0 and ft-1, inclusive, which is initialized to zero.  Let ftb
   be the location of the highest 1 bit in the two's-complement
   representation of (ft-1), or -1 if no bits are set.  If ftb>8, then
   the top 8 bits of t are decoded using t = ec_decode((ft-1>>ftb-8)+1),
   the decoder state is updated with the three-tuple (t,t+
   1,(ft-1>>ftb-8)+1), and the remaining bits are decoded with t =
   t<<ftb-8|ec_dec_bits(ftb-8).  If, at this point, t >= ft, then the
   current frame is corrupt.  In that case, the decoder should assume
   there has been an error in the coding, decoding, or transmission and
   SHOULD take measures to conceal the error and/or report to the
   application that a problem has occurred.  If the original value of
   ftb was not greater than 8, then t is decoded with t = ec_decode(ft),
   and the decoder state is updated with the three-tuple (t,t+1,ft).

4.1.5.  Current Bit Usage

   The bit allocation routines in CELT need to be able to determine a
   conservative upper bound on the number of bits that have been used
   from the current frame thus far.  This drives allocation decisions
   which must match those made in the encoder.  This is computed in the
   reference implementation to whole-bit precision by the function
   ec_tell() (entcode.h) and to fractional 1/8th bit precision by the
   function ec_tell_frac() (entcode.c).  Like all operations in the
   range coder, it must be implemented in a bit-exact manner, and must
   produce exactly the same value returned by the same functions in the
   encoder after encoding the same symbols.

4.2.  SILK Decoder

   At the receiving end, the received packets are by the range decoder
   split into a number of frames contained in the packet.  Each of which
   contains the necessary information to reconstruct a 20 ms frame of
   the output signal.






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4.2.1.  Decoder Modules

   An overview of the decoder is given in Figure 1.



      +---------+    +------------+
   -->| Range   |--->| Decode     |---------------------------+
    1 | Decoder | 2  | Parameters |----------+       5        |
      +---------+    +------------+     4    |                |
                          3 |                |                |
                           \/               \/               \/
                     +------------+   +------------+   +------------+
                     | Generate   |-->| LTP        |-->| LPC        |-->
                     | Excitation |   | Synthesis  |   | Synthesis  | 6
                     +------------+   +------------+   +------------+

   1: Range encoded bitstream
   2: Coded parameters
   3: Pulses and gains
   4: Pitch lags and LTP coefficients
   5: LPC coefficients
   6: Decoded signal


                          Decoder block diagram.

                                 Figure 1

4.2.1.1.  Range Decoder

   The range decoder decodes the encoded parameters from the received
   bitstream.  Output from this function includes the pulses and gains
   for the excitation signal generation, as well as LTP and LSF codebook
   indices, which are needed for decoding LTP and LPC coefficients
   needed for LTP and LPC synthesis filtering the excitation signal,
   respectively.

4.2.1.2.  Decode Parameters

   Pulses and gains are decoded from the parameters that were decoded by
   the range decoder.

   When a voiced frame is decoded and LTP codebook selection and indices
   are received, LTP coefficients are decoded using the selected
   codebook by choosing the vector that corresponds to the given
   codebook index in that codebook.  This is done for each of the four
   subframes.  The LPC coefficients are decoded from the LSF codebook by



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   first adding the chosen vectors, one vector from each stage of the
   codebook.  The resulting LSF vector is stabilized using the same
   method that was used in the encoder, see Section 5.2.7.5.  The LSF
   coefficients are then converted to LPC coefficients, and passed on to
   the LPC synthesis filter.

4.2.1.3.  Generate Excitation

   The pulses signal is multiplied with the quantization gain to create
   the excitation signal.

4.2.1.4.  LTP Synthesis

   For voiced speech, the excitation signal e(n) is input to an LTP
   synthesis filter that will recreate the long term correlation that
   was removed in the LTP analysis filter and generate an LPC excitation
   signal e_LPC(n), according to


                                     d
                                    __
                  e_LPC(n) = e(n) + \  e(n - L - i) * b_i,
                                    /_
                                   i=-d


   using the pitch lag L, and the decoded LTP coefficients b_i.  For
   unvoiced speech, the output signal is simply a copy of the excitation
   signal, i.e., e_LPC(n) = e(n).

4.2.1.5.  LPC Synthesis

   In a similar manner, the short-term correlation that was removed in
   the LPC analysis filter is recreated in the LPC synthesis filter.
   The LPC excitation signal e_LPC(n) is filtered using the LTP
   coefficients a_i, according to


                                   d_LPC
                                    __
                  y(n) = e_LPC(n) + \  e_LPC(n - i) * a_i,
                                    /_
                                    i=1


   where d_LPC is the LPC synthesis filter order, and y(n) is the
   decoded output signal.




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4.3.  CELT Decoder

   Insert decoder figure.

   +---------------+-----------------------------------+---------------+
   |   Symbol(s)   |                PDF                |   Condition   |
   +---------------+-----------------------------------+---------------+
   |    silence    |          [32767, 1]/32768         |               |
   |               |                                   |               |
   |  post-filter  |              [1, 1]/2             |               |
   |               |                                   |               |
   |     octave    |            uniform (6)            |  post-filter  |
   |               |                                   |               |
   |     period    |        raw bits (4+octave)        |  post-filter  |
   |               |                                   |               |
   |      gain     |            raw bits (3)           |  post-filter  |
   |               |                                   |               |
   |     tapset    |            [2, 1, 1]/4            |  post-filter  |
   |               |                                   |               |
   |   transient   |              [7, 1]/8             |               |
   |               |                                   |               |
   |     intra     |              [7, 1]/8             |               |
   |               |                                   |               |
   | coarse energy |           Section 4.3.2           |               |
   |               |                                   |               |
   |   tf_change   |           Section 4.3.1           |               |
   |               |                                   |               |
   |   tf_select   |              [1, 1]/2             | Section 4.3.1 |
   |               |                                   |               |
   |     spread    |          [7, 2, 21, 2]/32         |               |
   |               |                                   |               |
   |  dyn. alloc.  |           Section 4.3.3           |               |
   |               |                                   |               |
   |  alloc. trim  |  [2, 2, 5, 10, 22, 46, 22, 10, 5, |               |
   |               |             2, 2]/128             |               |
   |               |                                   |               |
   |      skip     |              [1, 1]/2             | Section 4.3.3 |
   |               |                                   |               |
   |   intensity   |              uniform              | Section 4.3.3 |
   |               |                                   |               |
   |      dual     |              [1, 1]/2             |               |
   |               |                                   |               |
   |  fine energy  |           Section 4.3.2           |               |
   |               |                                   |               |
   |    residual   |           Section 4.3.4           |               |
   |               |                                   |               |
   | anti-collapse |              [1, 1]/2             | Section 4.3.5 |
   |               |                                   |               |



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   |    finalize   |           Section 4.3.2           |               |
   +---------------+-----------------------------------+---------------+

        Order of the symbols in the CELT section of the bit-stream.

                                  Table 1

   The decoder extracts information from the range-coded bit-stream in
   the order described in the figure above.  In some circumstances, it
   is possible for a decoded value to be out of range due to a very
   small amount of redundancy in the encoding of large integers by the
   range coder.  In that case, the decoder should assume there has been
   an error in the coding, decoding, or transmission and SHOULD take
   measures to conceal the error and/or report to the application that a
   problem has occurred.

4.3.1.  Transient Decoding

   The _transient_ flag encoded in the bit-stream has a probability of
   1/8.  When it is set, then the MDCT coefficients represent multiple
   short MDCTs in the frame.  When not set, the coefficients represent a
   single long MDCT for the frame.  In addition to the global transient
   flag is a per-band binary flag to change the time-frequency (tf)
   resolution independently in each band.  The change in tf resolution
   is defined in tf_select_table[][] in celt.c and depends on the frame
   size, whether the transient flag is set, and the value of tf_select.
   The tf_select flag uses a 1/2 probability, but is only decoded if it
   can have an impact on the result knowing the value of all per-band
   tf_change flags.

4.3.2.  Energy Envelope Decoding

   It is important to quantize the energy with sufficient resolution
   because any energy quantization error cannot be compensated for at a
   later stage.  Regardless of the resolution used for encoding the
   shape of a band, it is perceptually important to preserve the energy
   in each band.  CELT uses a three-step coarse-fine-fine strategy for
   encoding the energy in the base-2 log domain, as implemented in
   quant_bands.c

4.3.2.1.  Coarse energy decoding

   Coarse quantization of the energy uses a fixed resolution of 6 dB
   (integer part of base-2 log).  To minimize the bitrate, prediction is
   applied both in time (using the previous frame) and in frequency
   (using the previous bands).  The part of the prediction that is based
   on the previous frame can be disabled, creating an "intra" frame
   where the energy is coded without reference to prior frames.  The



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   decoder first reads the intra flag to determine what prediction is
   used.  The 2-D z-transform of the prediction filter is: A(z_l,
   z_b)=(1-a*z_l^-1)*(1-z_b^-1)/(1-b*z_b^-1) where b is the band index
   and l is the frame index.  The prediction coefficients applied depend
   on the frame size in use when not using intra energy and a=0 b=4915/
   32768 when using intra energy.  The time-domain prediction is based
   on the final fine quantization of the previous frame, while the
   frequency domain (within the current frame) prediction is based on
   coarse quantization only (because the fine quantization has not been
   computed yet).  The prediction is clamped internally so that fixed
   point implementations with limited dynamic range to not suffer
   desynchronization.  We approximate the ideal probability distribution
   of the prediction error using a Laplace distribution with seperate
   parameters for each frame size in intra and inter-frame modes.  The
   coarse energy quantization is performed by unquant_coarse_energy()
   and unquant_coarse_energy_impl() (quant_bands.c).  The encoding of
   the Laplace-distributed values is implemented in ec_laplace_decode()
   (laplace.c).

4.3.2.2.  Fine energy quantization

   The number of bits assigned to fine energy quantization in each band
   is determined by the bit allocation computation described in
   Section 4.3.3.  Let B_i be the number of fine energy bits for band i;
   the refinement is an integer f in the range [0,2^B_i-1].  The mapping
   between f and the correction applied to the coarse energy is equal to
   (f+1/2)/2^B_i - 1/2.  Fine energy quantization is implemented in
   quant_fine_energy() (quant_bands.c).

   When some bits are left "unused" after all other flags have been
   decoded, these bits are assigned to a "final" step of fine
   allocation.  In effect, these bits are used to add one extra fine
   energy bit per band per channel.  The allocation process determines
   two _priorities_ for the final fine bits.  Any remaining bits are
   first assigned only to bands of priority 0, starting from band 0 and
   going up.  If all bands of priority 0 have received one bit per
   channel, then bands of priority 1 are assigned an extra bit per
   channel, starting from band 0.  If any bit is left after this, they
   are left unused.  This is implemented in unquant_energy_finalise()
   (quant_bands.c).

4.3.3.  Bit allocation

   Many codecs transmit significant amounts of side information for the
   purpose of controlling bit allocation within a frame.  Often this
   side information controls bit usage indirectly and must be carefully
   selected to achieve the desired rate constraints.




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   The band-energy normalized structure of Opus MDCT mode ensures that a
   constant bit allocation for the shape content of a band will result
   in a roughly constant tone to noise ratio, which provides for fairly
   consistent perceptual performance.  The effectiveness of this
   approach is the result of two factors: The band energy, which is
   understood to be perceptually important on its own, is always
   preserved regardless of the shape precision and because the constant
   tone-to-noise ratio implies a constant intra-band noise to masking
   ratio.  Intra-band masking is the strongest of the perceptual masking
   effects.  This structure means that the ideal allocation is more
   consistent from frame to frame than it is for other codecs without an
   equivalent structure.

   Because the bit allocation is used to drive the decoding of the
   range-coder stream it MUST be recovered exactly so that identical
   coding decisions are made in the encoder and decoder.  Any deviation
   from the reference's resulting bit allocation will result in
   corrupted output, though implementers are free to implement the
   procedure in any way which produces identical results.

   Because all of the information required to decode a frame must be
   derived from that frame alone in order to retain robustness to packet
   loss the overhead of explicitly signaling the allocation would be
   considerable, especially for low-latency (small frame size)
   applications, even though the allocation is relatively static.

   For this reason, in the MDCT mode Opus uses a primarily implicit bit
   allocation.  The available bit-stream capacity is known in advance to
   both the encoder and decoder without additional signaling, ultimately
   from the packet sizes expressed by a higher level protocol.  Using
   this information the codec interpolates an allocation from a hard-
   coded table.

   While the band-energy structure effectively models intra-band
   masking, it ignores the weaker inter-band masking, band-temporal
   masking, and other less significant perceptual effects.  While these
   effects can often be ignored they can become significant for
   particular samples.  One mechanism available to encoders would be to
   simply increase the overall rate for these frames, but this is not
   possible in a constant rate mode and can be fairly inefficient.  As a
   result three explicitly signaled mechanisms are provided to alter the
   implicit allocation:

   o  Band boost

   o  Allocation trim





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   o  band skipping

   The first of these mechanisms, band boost, allows an encoder to boost
   the allocation in specific bands.  The second, allocation trim, works
   by biasing the overall allocation towards higher or lower frequency
   bands.  The third, band skipping, selects which low-precision high
   frequency bands will be allocated no shape bits at all.

   In stereo mode there are also two additional parameters potentially
   coded as part of the allocation procedure: a parameter to allow the
   selective elimination of allocation for the 'side' in jointly coded
   bands, and a flag to deactivate joint coding.  These values are not
   signaled if they would be meaningless in the overall context of the
   allocation.

   Because every signaled adjustment increases overhead and
   implementation complexity none were included speculatively: The
   reference encoder makes use of all of these mechanisms.  While the
   decision logic in the reference was found to be effective enough to
   justify the overhead and complexity further analysis techniques may
   be discovered which increase the effectiveness of these parameters.
   As with other signaled parameters, encoder is free to choose the
   values in any manner but unless a technique is known to deliver
   superior perceptual results the methods used by the reference
   implementation should be used.

   The process of allocation consists of the following steps:
   determining the per-band maximum allocation vector, decoding the
   boosts, decoding the tilt, determining the remaining capacity the
   frame, searching the mode table for the entry nearest but not
   exceeding the available space (subject to the tilt, boosts, band
   maximums, and band minimums), linear interpolation, reallocation of
   unused bits with concurrent skip decoding, determination of the fine-
   energy vs shape split, and final reallocation.  This process results
   in an shape allocation per-band (in 1/8th bit units), a per-band
   fine-energy allocation (in 1 bit per channel units), a set of band
   priorities for controlling the use of remaining bits at the end of
   the frame, and a remaining balance of unallocated space which is
   usually zero except at very high rates.

   The maximum allocation vector is an approximation of the maximum
   space which can be used by each band for a given mode.  The value is
   approximate because the shape encoding is variable rate (due to
   entropy coding of splitting parameters).  Setting the maximum too low
   reduces the maximum achievable quality in a band while setting it too
   high may result in waste: bit-stream capacity available at the end of
   the frame which can not be put to any use.  The maximums specified by
   the codec reflect the average maximum.  In the reference the maximums



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   are provided partially computed form, in order to fit in less memory,
   as a static table (XXX cache.caps).  Implementations are expected to
   simply use the same table data but the procedure for generating this
   table is included in rate.c as part of compute_pulse_cache().

   To convert the values in cache.caps into the actual maximums: First
   set nbBands to the maximum number of bands for this mode and stereo
   to zero if stereo is not in use and one otherwise.  For each band
   assign N to the number of MDCT bins covered by the band (for one
   channel), set LM to the shift value for the frame size (e.g. 0 for
   120, 1 for 240, 3 for 480) then set i to nbBands*(2*LM+stereo).  Then
   set the maximum for the band to the i-th index of cache.caps + 64 and
   multiply by the number of channels in the current frame (one or two)
   and by N then divide the result by 4 using truncating integer
   division.  The resulting vector will be called cap[].  The elements
   fit in signed 16 bit integers but do not fit in 8 bits.  This
   procedure is implemented in the reference in the function init_caps()
   in celt.c.

   The band boosts are represented by a series of binary symbols which
   are coded with very low probability.  Each band can potentially be
   boosted multiple times, subject to the frame actually having enough
   room to obey the boost and having enough room to code the boost
   symbol.  The default coding cost for a boost starts out at six bits,
   but subsequent boosts in a band cost only a single bit and every time
   a band is boosted the initial cost is reduced (down to a minimum of
   two).  Since the initial cost of coding a boost is 6 bits the coding
   cost of the boost symbols when completely unused is 0.48 bits/frame
   for a 21 band mode (21*-log2(1-1/2^6)).

   To decode the band boosts: First set 'dynalloc_logp' to 6, the
   initial amount of storage required to signal a boost in bits,
   'total_bits' to the size of the frame in 8th-bits, 'total_boost' to
   zero, and 'tell' to the total number of 8th bits decoded so far.  For
   each band from the coding start (0 normally, but 17 in hybrid mode)
   to the coding end (which changes depending on the signaled
   bandwidth): Set 'width' to the number of MDCT bins in this band for
   all channels.  Take the larger of width and 64, then the minimum of
   that value and the width times eight and set 'quanta' to the result.
   This represents a boost step size of six bits subject to limits of
   1/bit/sample and 1/8th bit/sample.  Set 'boost' to zero and
   'dynalloc_loop_logp' to dynalloc_logp.  While dynalloc_loop_log (the
   current worst case symbol cost) in 8th bits plus tell is less than
   total_bits plus total_boost and boost is less than cap[] for this
   band: Decode a bit from the bitstream with a with dynalloc_loop_logp
   as the cost of a one, update tell to reflect the current used
   capacity, if the decoded value is zero break the loop otherwise add
   quanta to boost and total_boost, subtract quanta from total_bits, and



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   set dynalloc_loop_log to 1.  When the while loop finishes boost
   contains the boost for this band.  If boost is non-zero and
   dynalloc_logp is greater than 2 decrease dynalloc_logp.  Once this
   process has been execute on all bands the band boosts have been
   decoded.  This procedure is implemented around line 2352 of celt.c.

   At very low rates it's possible that there won't be enough available
   space to execute the inner loop even once.  In these cases band boost
   is not possible but its overhead is completely eliminated.  Because
   of the high cost of band boost when activated a reasonable encoder
   should not be using it at very low rates.  The reference implements
   its dynalloc decision logic at around 1269 of celt.c

   The allocation trim is a integer value from 0-10.  The default value
   of 5 indicates no trim.  The trim parameter is entropy coded in order
   to lower the coding cost of less extreme adjustments.  Values lower
   than 5 bias the allocation towards lower frequencies and values above
   5 bias it towards higher frequencies.  Like other signaled
   parameters, signaling of the trim is gated so that it is not included
   if there is insufficient space available in the bitstream.  To decode
   the trim first set the trim value to 5 then iff the count of decoded
   8th bits so far (ec_tell_frac) plus 48 (6 bits) is less than or equal
   to the total frame size in 8th bits minus total_boost (a product of
   the above band boost procedure) then decode the trim value using the
   inverse CDF {127, 126, 124, 119, 109, 87, 41, 19, 9, 4, 2, 0}.

   Stereo parameters

   Anti-collapse reservation

   The allocation computation first begins by setting up some initial
   conditions. 'total' is set to the available remaining 8th bits,
   computed by taking the size of the coded frame times 8 and
   subtracting ec_tell_frac().  From this value one (8th bit) is
   subtracted to assure that the resulting allocation will be
   conservative. 'anti_collapse_rsv' is set to 8 (8th bits) iff the
   frame is a transient, LM is greater than 1, and total is greater than
   or equal to (LM+2) * 8.  Total is then decremented by
   anti_collapse_rsv and clamped to be equal to or greater than zero.
   'skip_rsv' is set to 8 (8th bits) if total is greater than 8,
   otherwise it is zero.  Total is then decremented by skip_rsv.  This
   reserves space for the final skipping flag.

   If the current frame is stereo intensity_rsv is set to the
   conservative log2 in 8th bits of the number of coded bands for this
   frame (given by the table LOG2_FRAC_TABLE).  If intensity_rsv is
   greater than total then intensity_rsv is set to zero otherwise total
   is decremented by intensity_rsv, and if total is still greater than 8



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   dual_stereo_rsv is set to 8 and total is decremented by
   dual_stereo_rsv.

   The allocation process then computes a vector representing the hard
   minimum amounts allocation any band will receive for shape.  This
   minimum is higher than the technical limit of the PVQ process, but
   very low rate allocations produce excessively an sparse spectrum and
   these bands are better served by having no allocation at all.  For
   each coded band set thresh[band] to twenty-four times the number of
   MDCT bins in the band and divide by 16.  If 8 times the number of
   channels is greater, use that instead.  This sets the minimum
   allocation to one bit per channel or 48 128th bits per MDCT bin,
   whichever is greater.  The band size dependent part of this value is
   not scaled by the channel count because at the very low rates where
   this limit is applicable there will usually be no bits allocated to
   the side.

   The previously decoded allocation trim is used to derive a vector of
   per-band adjustments, 'trim_offsets[]'.  For each coded band take the
   alloc_trim and subtract 5 and LM then multiply the result by number
   of channels, the number MDCT bins in the shortest frame size for this
   mode, the number remaining bands, 2^LM, and 8.  Then divide this
   value by 64.  Finally, if the number of MDCT bins in the band per
   channel is only one 8 times the number of channels is subtracted in
   order to diminish the allocation by one bit because width 1 bands
   receive greater benefit from the coarse energy coding.

4.3.4.  Shape Decoder

   In each band, the normalized _shape_ is encoded using a vector
   quantization scheme called a "Pyramid vector quantizer".

   In the simplest case, the number of bits allocated in Section 4.3.3
   is converted to a number of pulses as described by Section 4.3.4.1.
   Knowing the number of pulses and the number of samples in the band,
   the decoder calculates the size of the codebook as detailed in
   Section 4.3.4.2.  The size is used to decode an unsigned integer
   (uniform probability model), which is the codeword index.  This index
   is converted into the corresponding vector as explained in
   Section 4.3.4.2.  This vector is then scaled to unit norm.

4.3.4.1.  Bits to Pulses

   Although the allocation is performed in 1/8th bit units, the
   quantization requires an integer number of pulses K. To do this, the
   encoder searches for the value of K that produces the number of bits
   that is the nearest to the allocated value (rounding down if exactly
   half-way between two values), subject to not exceeding the total



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   number of bits available.  For efficiency reasons the search is
   performed against a precomputated allocation table which only permits
   some K values for each N. The number of codebooks entries can be
   computed as explained in Section 5.3.5.2.  The difference between the
   number of bits allocated and the number of bits used is accumulated
   to a _balance_ (initialised to zero) that helps adjusting the
   allocation for the next bands.  One third of the balance is applied
   to the bit allocation of the each band to help achieving the target
   allocation.  The only exceptions are the band before the last and the
   last band, for which half the balance and the whole balance are
   applied, respectively.

4.3.4.2.  Index Decoding

   The codeword is decoded as a uniformly-distributed integer value by
   decode_pulses() (cwrs.c).  The codeword is converted from a unique
   index in the same way as specified in [PVQ].  The indexing is based
   on the calculation of V(N,K) (denoted N(L,K) in [PVQ]), which is the
   number of possible combinations of K pulses in N samples.  The number
   of combinations can be computed recursively as V(N,K) = V(N-1,K) +
   V(N,K-1) + V(N-1,K-1), with V(N,0) = 1 and V(0,K) = 0, K != 0.  There
   are many different ways to compute V(N,K), including pre-computed
   tables and direct use of the recursive formulation.  The reference
   implementation applies the recursive formulation one line (or column)
   at a time to save on memory use, along with an alternate, univariate
   recurrence to initialise an arbitrary line, and direct polynomial
   solutions for small N. All of these methods are equivalent, and have
   different trade-offs in speed, memory usage, and code size.
   Implementations MAY use any methods they like, as long as they are
   equivalent to the mathematical definition.

   The decoding of the codeword from the index is performed as specified
   in [PVQ], as implemented in function decode_pulses() (cwrs.c).

4.3.4.3.  Spreading

4.3.4.4.  Split decoding

   To avoid the need for multi-precision calculations when decoding PVQ
   codevectors, the maximum size allowed for codebooks is 32 bits.  When
   larger codebooks are needed, the vector is instead split in two sub-
   vectors of size N/2.  A quantized gain parameter with precision
   derived from the current allocation is entropy coded to represent the
   relative gains of each side of the split and the entire decoding
   process is recursively applied.  Multiple levels of splitting may be
   applied up to a frame size dependent limit.  The same recursive
   mechanism is applied for the joint coding of stereo audio.




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4.3.4.5.  Time-Frequency change

4.3.5.  Anti-collapse processing

   When the frame has the transient bit set...

4.3.6.  Denormalization

   Just like each band was normalized in the encoder, the last step of
   the decoder before the inverse MDCT is to denormalize the bands.
   Each decoded normalized band is multiplied by the square root of the
   decoded energy.  This is done by denormalise_bands() (bands.c).

4.3.7.  Inverse MDCT

   The inverse MDCT implementation has no special characteristics.  The
   input is N frequency-domain samples and the output is 2*N time-domain
   samples, while scaling by 1/2.  The output is windowed using the same
   window as the encoder.  The IMDCT and windowing are performed by
   mdct_backward (mdct.c).  If a time-domain pre-emphasis window was
   applied in the encoder, the (inverse) time-domain de-emphasis window
   is applied on the IMDCT result.

4.3.7.1.  Post-filter

   The output of the inverse MDCT (after weighted overlap-add) is sent
   to the post-filter.  Although the post-filter is applied at the end,
   the post-filter parameters are encoded at the beginning, just after
   the silence flag.  The post-filter can be switched on or off using
   one bit (logp=1).  If the post-filter is enabled, then the octave is
   decoded as an integer value between 0 and 6 of uniform probability.
   Once the octave is known, the fine pitch within the octave is decoded
   using 4+octave raw bits.  The final pitch period is equal to
   (16<<octave)+fine_pitch-1 so it is bounded between 15 and 1022,
   inclusively.  Next, the gain is decoded as three raw bits and is
   equal to G=3*(int_gain+1)/32.  The set of post-filter taps is decoded
   last using a pdf equal to [2, 1, 1]/4.  Tapset zero corresponds to
   the filter coefficients g0 = 0.3066406250, g1 = 0.2170410156, g2 =
   0.1296386719.  Tapset one corresponds to the filter coefficients g0 =
   0.4638671875, g1 = 0.2680664062, g2 = 0, and tapset two uses filter
   coefficients g0 = 0.7998046875, g1 = 0.1000976562, g2 = 0.

   The post-filter response is thus computed as:


             y(n) = x(n) + G*(g0*y(n-T) + g1*(y(n-T+1)+y(n-T+1))
                                        + g2*(y(n-T+2)+y(n-T+2)))




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   During a transition between different gains, a smooth transition is
   calculated using the square of the MDCT window.  It is important that
   values of y(n) be interpolated one at a time such that the past value
   of y(n) used is interpolated.

4.3.7.2.  De-emphasis

   After the post-filter, the signal is de-emphasized using the inverse
   of the pre-emphasis filter used in the encoder: 1/A(z)=1/
   (1-alpha_p*z^-1), where alpha_p=0.8500061035.

4.3.8.  Packet Loss Concealment (PLC)

   Packet loss concealment (PLC) is an optional decoder-side feature
   which SHOULD be included when transmitting over an unreliable
   channel.  Because PLC is not part of the bit-stream, there are
   several possible ways to implement PLC with different complexity/
   quality trade-offs.  The PLC in the reference implementation finds a
   periodicity in the decoded signal and repeats the windowed waveform
   using the pitch offset.  The windowed waveform is overlapped in such
   a way as to preserve the time-domain aliasing cancellation with the
   previous frame and the next frame.  This is implemented in
   celt_decode_lost() (mdct.c).




























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5.  Codec Encoder

   Opus encoder block diagram.


            +----------+    +-------+
            |  sample  |    | SILK  |
         +->|   rate   |--->|encoder|--+
         |  |conversion|    |       |  |
   audio |  +----------+    +-------+  |    +-------+
   ------+                             +--->| Range |
         |  +-------+                       |encoder|---->
         |  | CELT  |                  +--->|       | bit-stream
         +->|encoder|------------------+    +-------+
            |       |
            +-------+


5.1.  Range Coder

   The range coder also acts as the bit-packer for Opus.  It is used in
   three different ways, to encode:

   o  entropy-coded symbols with a fixed probability model using
      ec_encode(), (entenc.c)

   o  integers from 0 to 2^M-1 using ec_enc_uint() or ec_enc_bits(),
      (entenc.c)

   o  integers from 0 to N-1 (where N is not a power of two) using
      ec_enc_uint(). (entenc.c)

   The range encoder maintains an internal state vector composed of the
   four-tuple (low,rng,rem,ext), representing the low end of the current
   range, the size of the current range, a single buffered output octet,
   and a count of additional carry-propagating output octets.  Both rng
   and low are 32-bit unsigned integer values, rem is an octet value or
   the special value -1, and ext is an integer with at least 16 bits.
   This state vector is initialized at the start of each each frame to
   the value (0,2^31,-1,0).  The reference implementation re-uses the
   'val' field of the entropy coder structure to hold low, in order to
   allow the same structure to be used for encoding and decoding, but we
   maintain the distinction here for clarity.

5.1.1.  Encoding Symbols

   The main encoding function is ec_encode() (entenc.c), which takes as
   an argument a three-tuple (fl,fh,ft) describing the range of the



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   symbol to be encoded in the current context, with 0 <= fl < fh <= ft
   <= 65535.  The values of this tuple are derived from the probability
   model for the symbol.  Let f(i) be the frequency of the ith symbol in
   the current context.  Then the three-tuple corresponding to the kth
   symbol is given by fl=sum(f(i),i<k), fh=fl+f(i), and ft=sum(f(i)).

   ec_encode() updates the state of the encoder as follows.  If fl is
   greater than zero, then low = low + rng - (rng/ft)*(ft-fl) and rng =
   (rng/ft)*(fh-fl).  Otherwise, low is unchanged and rng = rng - (rng/
   ft)*(fh-fl).  The divisions here are exact integer division.  After
   this update, the range is normalized.

   To normalize the range, the following process is repeated until rng >
   2^23.  First, the top 9 bits of low, (low>>23), are placed into a
   carry buffer.  Then, low is set to (low << 8 & 0x7FFFFFFF) and rng is
   set to (rng<<8).  This process is carried out by ec_enc_normalize()
   (entenc.c).

   The 9 bits produced in each iteration of the normalization loop
   consist of 8 data bits and a carry flag.  The final value of the
   output bits is not determined until carry propagation is accounted
   for.  Therefore the reference implementation buffers a single (non-
   propagating) output octet and keeps a count of additional propagating
   (0xFF) output octets.  An implementation MAY choose to use any
   mathematically equivalent scheme to perform carry propagation.

   The function ec_enc_carry_out() (entenc.c) performs this buffering.
   It takes a 9-bit input value, c, from the normalization: 8 bits of
   output and a carry bit.  If c is 0xFF, then ext is incremented and no
   octets are output.  Otherwise, if rem is not the special value -1,
   then the octet (rem+(c>>8)) is output.  Then ext octets are output
   with the value 0 if the carry bit is set, or 0xFF if it is not, and
   rem is set to the lower 8 bits of c.  After this, ext is set to zero.

   In the reference implementation, a special version of ec_encode()
   called ec_encode_bin() (entenc.c) is defined to take a two-tuple
   (fl,ftb), where 0 <= fl < 2^ftb and ftb < 16.  It is mathematically
   equivalent to calling ec_encode() with the three-tuple (fl,fl+
   1,1<<ftb), but avoids using division.

5.1.2.  Encoding Raw Bits

   The CELT layer also allows directly encoding a series of raw bits,
   outside of the range coder, implemented in ec_enc_bits() (entenc.c).
   The raw bits are packed at the end of the packet, starting by storing
   the least significant bit of the value to be packed in the least
   significant bit of the last byte, filling up to the most significant
   bit in the last byte, and the continuing in the least significant bit



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   of the penultimate byte, and so on.  This packing may continue into
   the last byte output by the range coder, though the format should
   render it impossible to overwrite any set bit produced by the range
   coder when the procedure in Section 5.1.4 is followed to finalize the
   stream.

5.1.3.  Encoding Uniformly Distributed Integers

   The function ec_enc_uint() is based on ec_encode() and encodes one of
   N equiprobable symbols, each with a frequency of 1, where N may be as
   large as 2^32-1.  Because ec_encode() is limited to a total frequency
   of 2^16-1, this is done by encoding a series of symbols in smaller
   contexts.

   ec_enc_uint() (entenc.c) takes a two-tuple (fl,ft), where ft is not
   necessarily a power of two.  Let ftb be the location of the highest 1
   bit in the two's-complement representation of (ft-1), or -1 if no
   bits are set.  If ftb>8, then the top 8 bits of fl are encoded using
   ec_encode() with the three-tuple (fl>>ftb-8,(fl>>ftb-8)+
   1,(ft-1>>ftb-8)+1), and the remaining bits are encoded as raw bits.
   Otherwise, fl is encoded with ec_encode() directly using the three-
   tuple (fl,fl+1,ft).

5.1.4.  Finalizing the Stream

   After all symbols are encoded, the stream must be finalized by
   outputting a value inside the current range.  Let end be the integer
   in the interval [low,low+rng) with the largest number of trailing
   zero bits, b, such that end+(1<<b)-1 is also in the interval
   [low,low+rng).  Then while end is not zero, the top 9 bits of end,
   e.g., (end>>23), are sent to the carry buffer, and end is replaced by
   (end<<8&0x7FFFFFFF).  Finally, if the value in carry buffer, rem, is
   neither zero nor the special value -1, or the carry count, ext, is
   greater than zero, then 9 zero bits are sent to the carry buffer.
   After the carry buffer is finished outputting octets, the rest of the
   output buffer (if any) is padded with zero bits, until it reaches the
   raw bits.  Finally, rem is set to the special value -1.  This process
   is implemented by ec_enc_done() (entenc.c).

5.1.5.  Current Bit Usage

   The bit allocation routines in Opus need to be able to determine a
   conservative upper bound on the number of bits that have been used to
   encode the current frame thus far.  This drives allocation decisions
   and ensures that the range coder and raw bits will not overflow the
   output buffer.  This is computed in the reference implementation to
   whole-bit precision by the function ec_tell() (entcode.h) and to
   fractional 1/8th bit precision by the function ec_tell_frac()



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   (entcode.c).  Like all operations in the range coder, it must be
   implemented in a bit-exact manner, and must produce exactly the same
   value returned by the same functions in the decoder after decoding
   the same symbols.

5.2.  SILK Encoder

   In the following, we focus on the core encoder and describe its
   components.  For simplicity, we will refer to the core encoder simply
   as the encoder in the remainder of this document.  An overview of the
   encoder is given in Figure 2.


                                                                 +---+
                                  +----------------------------->|   |
           +---------+            |     +---------+              |   |
           |Voice    |            |     |LTP      |              |   |
    +----->|Activity |-----+      +---->|Scaling  |---------+--->|   |
    |      |Detector |  3  |      |     |Control  |<+  12   |    |   |
    |      +---------+     |      |     +---------+ |       |    |   |
    |                      |      |     +---------+ |       |    |   |
    |                      |      |     |Gains    | |  11   |    |   |
    |                      |      |  +->|Processor|-|---+---|--->| R |
    |                      |      |  |  |         | |   |   |    | a |
    |                     \/      |  |  +---------+ |   |   |    | n |
    |                 +---------+ |  |  +---------+ |   |   |    | g |
    |                 |Pitch    | |  |  |LSF      | |   |   |    | e |
    |              +->|Analysis |-+  |  |Quantizer|-|---|---|--->|   |
    |              |  |         |4|  |  |         | | 8 |   |    | E |->
    |              |  +---------+ |  |  +---------+ |   |   |    | n |14
    |              |              |  |   9/\  10|   |   |   |    | c |
    |              |              |  |    |    \/   |   |   |    | o |
    |              |  +---------+ |  |  +----------+|   |   |    | d |
    |              |  |Noise    | +--|->|Prediction|+---|---|--->| e |
    |              +->|Shaping  |-|--+  |Analysis  || 7 |   |    | r |
    |              |  |Analysis |5|  |  |          ||   |   |    |   |
    |              |  +---------+ |  |  +----------+|   |   |    |   |
    |              |              |  |       /\     |   |   |    |   |
    |              |    +---------|--|-------+      |   |   |    |   |
    |              |    |        \/  \/            \/  \/  \/    |   |
    |  +---------+ |    |      +---------+       +------------+  |   |
    |  |High-Pass| |    |      |         |       |Noise       |  |   |
   -+->|Filter   |-+----+----->|Prefilter|------>|Shaping     |->|   |
   1   |         |      2      |         |   6   |Quantization|13|   |
       +---------+             +---------+       +------------+  +---+

   1:  Input speech signal
   2:  High passed input signal



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   3:  Voice activity estimate
   4:  Pitch lags (per 5 ms) and voicing decision (per 20 ms)
   5:  Noise shaping quantization coefficients
     - Short term synthesis and analysis
       noise shaping coefficients (per 5 ms)
     - Long term synthesis and analysis noise
       shaping coefficients (per 5 ms and for voiced speech only)
     - Noise shaping tilt (per 5 ms)
     - Quantizer gain/step size (per 5 ms)
   6:  Input signal filtered with analysis noise shaping filters
   7:  Short and long term prediction coefficients
       LTP (per 5 ms) and LPC (per 20 ms)
   8:  LSF quantization indices
   9:  LSF coefficients
   10: Quantized LSF coefficients
   11: Processed gains, and synthesis noise shape coefficients
   12: LTP state scaling coefficient. Controlling error propagation
      / prediction gain trade-off
   13: Quantized signal
   14: Range encoded bitstream



                          Encoder block diagram.

                                 Figure 2

5.2.1.  Voice Activity Detection

   The input signal is processed by a VAD (Voice Activity Detector) to
   produce a measure of voice activity, and also spectral tilt and
   signal-to-noise estimates, for each frame.  The VAD uses a sequence
   of half-band filterbanks to split the signal in four subbands: 0 -
   Fs/16, Fs/16 - Fs/8, Fs/8 - Fs/4, and Fs/4 - Fs/2, where Fs is the
   sampling frequency, that is, 8, 12, 16 or 24 kHz.  The lowest
   subband, from 0 - Fs/16 is high-pass filtered with a first-order MA
   (Moving Average) filter (with transfer function H(z) = 1-z^(-1)) to
   reduce the energy at the lowest frequencies.  For each frame, the
   signal energy per subband is computed.  In each subband, a noise
   level estimator tracks the background noise level and an SNR (Signal-
   to-Noise Ratio) value is computed as the logarithm of the ratio of
   energy to noise level.  Using these intermediate variables, the
   following parameters are calculated for use in other SILK modules:

   o  Average SNR.  The average of the subband SNR values.

   o  Smoothed subband SNRs.  Temporally smoothed subband SNR values.




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   o  Speech activity level.  Based on the average SNR and a weighted
      average of the subband energies.

   o  Spectral tilt.  A weighted average of the subband SNRs, with
      positive weights for the low subbands and negative weights for the
      high subbands.

5.2.2.  High-Pass Filter

   The input signal is filtered by a high-pass filter to remove the
   lowest part of the spectrum that contains little speech energy and
   may contain background noise.  This is a second order ARMA (Auto
   Regressive Moving Average) filter with a cut-off frequency around 70
   Hz.

   In the future, a music detector may also be used to lower the cut-off
   frequency when the input signal is detected to be music rather than
   speech.

5.2.3.  Pitch Analysis

   The high-passed input signal is processed by the open loop pitch
   estimator shown in Figure 3.




























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                                    +--------+  +----------+
                                    |2 x Down|  |Time-     |
                                 +->|sampling|->|Correlator|     |
                                 |  |        |  |          |     |4
                                 |  +--------+  +----------+    \/
                                 |                    | 2    +-------+
                                 |                    |  +-->|Speech |5
       +---------+    +--------+ |                   \/  |   |Type   |->
       |LPC      |    |Down    | |              +----------+ |       |
    +->|Analysis | +->|sample  |-+------------->|Time-     | +-------+
    |  |         | |  |to 8 kHz|                |Correlator|----------->
    |  +---------+ |  +--------+                |__________|          6
    |       |      |                                  |3
    |      \/      |                                 \/
    |  +---------+ |                            +----------+
    |  |Whitening| |                            |Time-     |
   -+->|Filter   |-+--------------------------->|Correlator|----------->
   1   |         |                              |          |          7
       +---------+                              +----------+

   1: Input signal
   2: Lag candidates from stage 1
   3: Lag candidates from stage 2
   4: Correlation threshold
   5: Voiced/unvoiced flag
   6: Pitch correlation
   7: Pitch lags


                   Block diagram of the pitch estimator.

                                 Figure 3

   The pitch analysis finds a binary voiced/unvoiced classification,
   and, for frames classified as voiced, four pitch lags per frame - one
   for each 5 ms subframe - and a pitch correlation indicating the
   periodicity of the signal.  The input is first whitened using a
   Linear Prediction (LP) whitening filter, where the coefficients are
   computed through standard Linear Prediction Coding (LPC) analysis.
   The order of the whitening filter is 16 for best results, but is
   reduced to 12 for medium complexity and 8 for low complexity modes.
   The whitened signal is analyzed to find pitch lags for which the time
   correlation is high.  The analysis consists of three stages for
   reducing the complexity:

   o  In the first stage, the whitened signal is downsampled to 4 kHz
      (from 8 kHz) and the current frame is correlated to a signal
      delayed by a range of lags, starting from a shortest lag



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      corresponding to 500 Hz, to a longest lag corresponding to 56 Hz.

   o  The second stage operates on a 8 kHz signal ( downsampled from 12,
      16 or 24 kHz ) and measures time correlations only near the lags
      corresponding to those that had sufficiently high correlations in
      the first stage.  The resulting correlations are adjusted for a
      small bias towards short lags to avoid ending up with a multiple
      of the true pitch lag.  The highest adjusted correlation is
      compared to a threshold depending on:

      *  Whether the previous frame was classified as voiced

      *  The speech activity level

      *  The spectral tilt.

      If the threshold is exceeded, the current frame is classified as
      voiced and the lag with the highest adjusted correlation is stored
      for a final pitch analysis of the highest precision in the third
      stage.

   o  The last stage operates directly on the whitened input signal to
      compute time correlations for each of the four subframes
      independently in a narrow range around the lag with highest
      correlation from the second stage.

5.2.4.  Noise Shaping Analysis

   The noise shaping analysis finds gains and filter coefficients used
   in the prefilter and noise shaping quantizer.  These parameters are
   chosen such that they will fulfil several requirements:

   o  Balancing quantization noise and bitrate.  The quantization gains
      determine the step size between reconstruction levels of the
      excitation signal.  Therefore, increasing the quantization gain
      amplifies quantization noise, but also reduces the bitrate by
      lowering the entropy of the quantization indices.

   o  Spectral shaping of the quantization noise; the noise shaping
      quantizer is capable of reducing quantization noise in some parts
      of the spectrum at the cost of increased noise in other parts
      without substantially changing the bitrate.  By shaping the noise
      such that it follows the signal spectrum, it becomes less audible.
      In practice, best results are obtained by making the shape of the
      noise spectrum slightly flatter than the signal spectrum.

   o  Deemphasizing spectral valleys; by using different coefficients in
      the analysis and synthesis part of the prefilter and noise shaping



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      quantizer, the levels of the spectral valleys can be decreased
      relative to the levels of the spectral peaks such as speech
      formants and harmonics.  This reduces the entropy of the signal,
      which is the difference between the coded signal and the
      quantization noise, thus lowering the bitrate.

   o  Matching the levels of the decoded speech formants to the levels
      of the original speech formants; an adjustment gain and a first
      order tilt coefficient are computed to compensate for the effect
      of the noise shaping quantization on the level and spectral tilt.



                 / \   ___
                  |   // \\
                  |  //   \\     ____
                  |_//     \\___//  \\         ____
                  | /  ___  \   /    \\       //  \\
                P |/  /   \  \_/      \\_____//    \\
                o |  /     \     ____  \     /      \\
                w | /       \___/    \  \___/  ____  \\___ 1
                e |/                  \       /    \  \
                r |                    \_____/      \  \__ 2
                  |                                  \
                  |                                   \___ 3
                  |
                  +---------------------------------------->
                                   Frequency

               1: Input signal spectrum
               2: Deemphasized and level matched spectrum
               3: Quantization noise spectrum


           Noise shaping and spectral de-emphasis illustration.

                                 Figure 4

   Figure 4 shows an example of an input signal spectrum (1).  After de-
   emphasis and level matching, the spectrum has deeper valleys (2).
   The quantization noise spectrum (3) more or less follows the input
   signal spectrum, while having slightly less pronounced peaks.  The
   entropy, which provides a lower bound on the bitrate for encoding the
   excitation signal, is proportional to the area between the
   deemphasized spectrum (2) and the quantization noise spectrum (3).
   Without de-emphasis, the entropy is proportional to the area between
   input spectrum (1) and quantization noise (3) - clearly higher.




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   The transformation from input signal to deemphasized signal can be
   described as a filtering operation with a filter


                                                    Wana(z)
               H(z) = G * ( 1 - c_tilt * z^(-1) ) * -------
                                                    Wsyn(z),


   having an adjustment gain G, a first order tilt adjustment filter
   with tilt coefficient c_tilt, and where


                   16                                 d
                   __                                __
    Wana(z) = (1 - \ (a_ana(k) * z^(-k))*(1 - z^(-L) \ b_ana(k)*z^(-k)),
                   /_                                /_
                   k=1                               k=-d


   is the analysis part of the de-emphasis filter, consisting of the
   short-term shaping filter with coefficients a_ana(k), and the long-
   term shaping filter with coefficients b_ana(k) and pitch lag L. The
   parameter d determines the number of long-term shaping filter taps.

   Similarly, but without the tilt adjustment, the synthesis part can be
   written as


                   16                                 d
                   __                                __
    Wsyn(z) = (1 - \ (a_syn(k) * z^(-k))*(1 - z^(-L) \ b_syn(k)*z^(-k)).
                   /_                                /_
                   k=1                               k=-d


   All noise shaping parameters are computed and applied per subframe of
   5 milliseconds.  First, an LPC analysis is performed on a windowed
   signal block of 15 milliseconds.  The signal block has a look-ahead
   of 5 milliseconds relative to the current subframe, and the window is
   an asymmetric sine window.  The LPC analysis is done with the
   autocorrelation method, with an order of 16 for best quality or 12 in
   low complexity operation.  The quantization gain is found as the
   square-root of the residual energy from the LPC analysis, multiplied
   by a value inversely proportional to the coding quality control
   parameter and the pitch correlation.

   Next we find the two sets of short-term noise shaping coefficients



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   a_ana(k) and a_syn(k), by applying different amounts of bandwidth
   expansion to the coefficients found in the LPC analysis.  This
   bandwidth expansion moves the roots of the LPC polynomial towards the
   origo, using the formulas


                         a_ana(k) = a(k)*g_ana^k, and
                         a_syn(k) = a(k)*g_syn^k,


   where a(k) is the k'th LPC coefficient and the bandwidth expansion
   factors g_ana and g_syn are calculated as


                         g_ana = 0.94 - 0.02*C, and
                         g_syn = 0.94 + 0.02*C,


   where C is the coding quality control parameter between 0 and 1.
   Applying more bandwidth expansion to the analysis part than to the
   synthesis part gives the desired de-emphasis of spectral valleys in
   between formants.

   The long-term shaping is applied only during voiced frames.  It uses
   three filter taps, described by


                   b_ana = F_ana * [0.25, 0.5, 0.25], and
                   b_syn = F_syn * [0.25, 0.5, 0.25].


   For unvoiced frames these coefficients are set to 0.  The
   multiplication factors F_ana and F_syn are chosen between 0 and 1,
   depending on the coding quality control parameter, as well as the
   calculated pitch correlation and smoothed subband SNR of the lowest
   subband.  By having F_ana less than F_syn, the pitch harmonics are
   emphasized relative to the valleys in between the harmonics.

   The tilt coefficient c_tilt is for unvoiced frames chosen as


                          c_tilt = 0.4, and as
                          c_tilt = 0.04 + 0.06 * C


   for voiced frames, where C again is the coding quality control
   parameter and is between 0 and 1.




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   The adjustment gain G serves to correct any level mismatch between
   original and decoded signal that might arise from the noise shaping
   and de-emphasis.  This gain is computed as the ratio of the
   prediction gain of the short-term analysis and synthesis filter
   coefficients.  The prediction gain of an LPC synthesis filter is the
   square-root of the output energy when the filter is excited by a
   unit-energy impulse on the input.  An efficient way to compute the
   prediction gain is by first computing the reflection coefficients
   from the LPC coefficients through the step-down algorithm, and
   extracting the prediction gain from the reflection coefficients as


                                 K
                                ___
                   predGain = ( | | 1 - (r_k)^2 )^(-0.5),
                                k=1


   where r_k is the k'th reflection coefficient.

   Initial values for the quantization gains are computed as the square-
   root of the residual energy of the LPC analysis, adjusted by the
   coding quality control parameter.  These quantization gains are later
   adjusted based on the results of the prediction analysis.

5.2.5.  Prefilter

   In the prefilter the input signal is filtered using the spectral
   valley de-emphasis filter coefficients from the noise shaping
   analysis, see Section 5.2.4.  By applying only the noise shaping
   analysis filter to the input signal, it provides the input to the
   noise shaping quantizer.

5.2.6.  Prediction Analysis

   The prediction analysis is performed in one of two ways depending on
   how the pitch estimator classified the frame.  The processing for
   voiced and unvoiced speech are described in Section 5.2.6.1 and
   Section 5.2.6.2, respectively.  Inputs to this function include the
   pre-whitened signal from the pitch estimator, see Section 5.2.3.

5.2.6.1.  Voiced Speech

   For a frame of voiced speech the pitch pulses will remain dominant in
   the pre-whitened input signal.  Further whitening is desirable as it
   leads to higher quality at the same available bit-rate.  To achieve
   this, a Long-Term Prediction (LTP) analysis is carried out to
   estimate the coefficients of a fifth order LTP filter for each of



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   four sub-frames.  The LTP coefficients are used to find an LTP
   residual signal with the simulated output signal as input to obtain
   better modelling of the output signal.  This LTP residual signal is
   the input to an LPC analysis where the LPCs are estimated using Burgs
   method, such that the residual energy is minimized.  The estimated
   LPCs are converted to a Line Spectral Frequency (LSF) vector, and
   quantized as described in Section 5.2.7.  After quantization, the
   quantized LSF vector is converted to LPC coefficients and hence by
   using these quantized coefficients the encoder remains fully
   synchronized with the decoder.  The LTP coefficients are quantized
   using a method described in Section 5.2.8.  The quantized LPC and LTP
   coefficients are now used to filter the high-pass filtered input
   signal and measure a residual energy for each of the four subframes.

5.2.6.2.  Unvoiced Speech

   For a speech signal that has been classified as unvoiced there is no
   need for LTP filtering as it has already been determined that the
   pre-whitened input signal is not periodic enough within the allowed
   pitch period range for an LTP analysis to be worth-while the cost in
   terms of complexity and rate.  Therefore, the pre-whitened input
   signal is discarded and instead the high-pass filtered input signal
   is used for LPC analysis using Burgs method.  The resulting LPC
   coefficients are converted to an LSF vector, quantized as described
   in the following section and transformed back to obtain quantized LPC
   coefficients.  The quantized LPC coefficients are used to filter the
   high-pass filtered input signal and measure a residual energy for
   each of the four subframes.

5.2.7.  LSF Quantization

   The purpose of quantization in general is to significantly lower the
   bit rate at the cost of some introduced distortion.  A higher rate
   should always result in lower distortion, and lowering the rate will
   generally lead to higher distortion.  A commonly used but generally
   sub-optimal approach is to use a quantization method with a constant
   rate where only the error is minimized when quantizing.

5.2.7.1.  Rate-Distortion Optimization

   Instead, we minimize an objective function that consists of a
   weighted sum of rate and distortion, and use a codebook with an
   associated non-uniform rate table.  Thus, we take into account that
   the probability mass function for selecting the codebook entries are
   by no means guaranteed to be uniform in our scenario.  The advantage
   of this approach is that it ensures that rarely used codebook vector
   centroids, which are modelling statistical outliers in the training
   set can be quantized with a low error but with a relatively high cost



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   in terms of a high rate.  At the same time this approach also
   provides the advantage that frequently used centroids are modelled
   with low error and a relatively low rate.  This approach will lead to
   equal or lower distortion than the fixed rate codebook at any given
   average rate, provided that the data is similar to the data used for
   training the codebook.

5.2.7.2.  Error Mapping

   Instead of minimizing the error in the LSF domain, we map the errors
   to better approximate spectral distortion by applying an individual
   weight to each element in the error vector.  The weight vectors are
   calculated for each input vector using the Inverse Harmonic Mean
   Weighting (IHMW) function proposed by Laroia et al., see
   [laroia-icassp].  Consequently, we solve the following minimization
   problem, i.e.,


         LSF_q = argmin { (LSF - c)' * W * (LSF - c) + mu * rate },
                 c in C


   where LSF_q is the quantized vector, LSF is the input vector to be
   quantized, and c is the quantized LSF vector candidate taken from the
   set C of all possible outcomes of the codebook.

5.2.7.3.  Multi-Stage Vector Codebook

   We arrange the codebook in a multiple stage structure to achieve a
   quantizer that is both memory efficient and highly scalable in terms
   of computational complexity, see e.g. [sinervo-norsig].  In the first
   stage the input is the LSF vector to be quantized, and in any other
   stage s > 1, the input is the quantization error from the previous
   stage, see Figure 5.

















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         Stage 1:           Stage 2:                Stage S:
       +----------+       +----------+            +----------+
       |  c_{1,1} |       |  c_{2,1} |            |  c_{S,1} |
   LSF +----------+ res_1 +----------+  res_{S-1} +----------+
   --->|  c_{1,2} |------>|  c_{2,2} |--> ... --->|  c_{S,2} |--->
       +----------+       +----------+            +----------+ res_S =
           ...                ...                     ...      LSF-LSF_q
       +----------+       +----------+            +----------+
       |c_{1,M1-1}|       |c_{2,M2-1}|            |c_{S,MS-1}|
       +----------+       +----------+            +----------+
       | c_{1,M1} |       | c_{2,M2} |            | c_{S,MS} |
       +----------+       +----------+            +----------+


                Multi-Stage LSF Vector Codebook Structure.

                                 Figure 5

   By storing total of M codebook vectors, i.e.,


                                      S
                                     __
                                 M = \  Ms,
                                     /_
                                     s=1


   where M_s is the number of vectors in stage s, we obtain a total of


                                      S
                                     ___
                                 T = | | Ms
                                     s=1


   possible combinations for generating the quantized vector.  It is for
   example possible to represent 2^36 uniquely combined vectors using
   only 216 vectors in memory, as done in SILK for voiced speech at all
   sample frequencies above 8 kHz.

5.2.7.4.  Survivor Based Codebook Search

   This number of possible combinations is far too high for a full
   search to be carried out for each frame so for all stages but the
   last, i.e., s smaller than S, only the best min( L, Ms ) centroids
   are carried over to stage s+1.  In each stage the objective function,



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   i.e., the weighted sum of accumulated bit-rate and distortion, is
   evaluated for each codebook vector entry and the results are sorted.
   Only the best paths and the corresponding quantization errors are
   considered in the next stage.  In the last stage S the single best
   path through the multistage codebook is determined.  By varying the
   maximum number of survivors from each stage to the next L, the
   complexity can be adjusted in real-time at the cost of a potential
   increase when evaluating the objective function for the resulting
   quantized vector.  This approach scales all the way between the two
   extremes, L=1 being a greedy search, and the desirable but infeasible
   full search, L=T/MS.  In fact, a performance almost as good as what
   can be achieved with the infeasible full search can be obtained at a
   substantially lower complexity by using this approach, see e.g.
   [leblanc-tsap].

5.2.7.5.  LSF Stabilization

   If the input is stable, finding the best candidate will usually
   result in the quantized vector also being stable, but due to the
   multi-stage approach it could in theory happen that the best
   quantization candidate is unstable and because of this there is a
   need to explicitly ensure that the quantized vectors are stable.
   Therefore we apply a LSF stabilization method which ensures that the
   LSF parameters are within valid range, increasingly sorted, and have
   minimum distances between each other and the border values that have
   been pre-determined as the 0.01 percentile distance values from a
   large training set.

5.2.7.6.  Off-Line Codebook Training

   The vectors and rate tables for the multi-stage codebook have been
   trained by minimizing the average of the objective function for LSF
   vectors from a large training set.

5.2.8.  LTP Quantization

   For voiced frames, the prediction analysis described in
   Section 5.2.6.1 resulted in four sets (one set per subframe) of five
   LTP coefficients, plus four weighting matrices.  Also, the LTP
   coefficients for each subframe are quantized using entropy
   constrained vector quantization.  A total of three vector codebooks
   are available for quantization, with different rate-distortion trade-
   offs.  The three codebooks have 10, 20 and 40 vectors and average
   rates of about 3, 4, and 5 bits per vector, respectively.
   Consequently, the first codebook has larger average quantization
   distortion at a lower rate, whereas the last codebook has smaller
   average quantization distortion at a higher rate.  Given the
   weighting matrix W_ltp and LTP vector b, the weighted rate-distortion



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   measure for a codebook vector cb_i with rate r_i is give by


               RD = u * (b - cb_i)' * W_ltp * (b - cb_i) + r_i,


   where u is a fixed, heuristically-determined parameter balancing the
   distortion and rate.  Which codebook gives the best performance for a
   given LTP vector depends on the weighting matrix for that LTP vector.
   For example, for a low valued W_ltp, it is advantageous to use the
   codebook with 10 vectors as it has a lower average rate.  For a large
   W_ltp, on the other hand, it is often better to use the codebook with
   40 vectors, as it is more likely to contain the best codebook vector.
   The weighting matrix W_ltp depends mostly on two aspects of the input
   signal.  The first is the periodicity of the signal; the more
   periodic the larger W_ltp.  The second is the change in signal energy
   in the current subframe, relative to the signal one pitch lag
   earlier.  A decaying energy leads to a larger W_ltp than an
   increasing energy.  Both aspects do not fluctuate very fast which
   causes the W_ltp matrices for different subframes of one frame often
   to be similar.  As a result, one of the three codebooks typically
   gives good performance for all subframes.  Therefore the codebook
   search for the subframe LTP vectors is constrained to only allow
   codebook vectors to be chosen from the same codebook, resulting in a
   rate reduction.

   To find the best codebook, each of the three vector codebooks is used
   to quantize all subframe LTP vectors and produce a combined weighted
   rate-distortion measure for each vector codebook and the vector
   codebook with the lowest combined rate-distortion over all subframes
   is chosen.  The quantized LTP vectors are used in the noise shaping
   quantizer, and the index of the codebook plus the four indices for
   the four subframe codebook vectors are passed on to the range
   encoder.

5.2.9.  Noise Shaping Quantizer

   The noise shaping quantizer independently shapes the signal and
   coding noise spectra to obtain a perceptually higher quality at the
   same bitrate.

   The prefilter output signal is multiplied with a compensation gain G
   computed in the noise shaping analysis.  Then the output of a
   synthesis shaping filter is added, and the output of a prediction
   filter is subtracted to create a residual signal.  The residual
   signal is multiplied by the inverse quantized quantization gain from
   the noise shaping analysis, and input to a scalar quantizer.  The
   quantization indices of the scalar quantizer represent a signal of



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   pulses that is input to the pyramid range encoder.  The scalar
   quantizer also outputs a quantization signal, which is multiplied by
   the quantized quantization gain from the noise shaping analysis to
   create an excitation signal.  The output of the prediction filter is
   added to the excitation signal to form the quantized output signal
   y(n).  The quantized output signal y(n) is input to the synthesis
   shaping and prediction filters.

5.2.10.  Range Encoder

   Range encoding is a well known method for entropy coding in which a
   bitstream sequence is continually updated with every new symbol,
   based on the probability for that symbol.  It is similar to
   arithmetic coding but rather than being restricted to generating
   binary output symbols, it can generate symbols in any chosen number
   base.  In SILK all side information is range encoded.  Each quantized
   parameter has its own cumulative density function based on histograms
   for the quantization indices obtained by running a training database.

5.2.10.1.  Bitstream Encoding Details

   TBD.

5.3.  CELT Encoder

   Copy from CELT draft.

5.3.1.  Pre-filter

   Inverse of the post-filter

5.3.2.  Forward MDCT

   The MDCT implementation has no special characteristics.  The input is
   a windowed signal (after pre-emphasis) of 2*N samples and the output
   is N frequency-domain samples.  A _low-overlap_ window is used to
   reduce the algorithmic delay.  It is derived from a basic (full
   overlap) window that is the same as the one used in the Vorbis codec:
   W(n)=[sin(pi/2*sin(pi/2*(n+.5)/L))]^2.  The low-overlap window is
   created by zero-padding the basic window and inserting ones in the
   middle, such that the resulting window still satisfies power
   complementarity.  The MDCT is computed in mdct_forward() (mdct.c),
   which includes the windowing operation and a scaling of 2/N.

5.3.3.  Bands and Normalization

   The MDCT output is divided into bands that are designed to match the
   ear's critical bands for the smallest (2.5ms) frame size.  The larger



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   frame sizes use integer multiplies of the 2.5ms layout.  For each
   band, the encoder computes the energy that will later be encoded.
   Each band is then normalized by the square root of the *non-
   quantized* energy, such that each band now forms a unit vector X. The
   energy and the normalization are computed by compute_band_energies()
   and normalise_bands() (bands.c), respectively.

5.3.4.  Energy Envelope Quantization

   It is important to quantize the energy with sufficient resolution
   because any energy quantization error cannot be compensated for at a
   later stage.  Regardless of the resolution used for encoding the
   shape of a band, it is perceptually important to preserve the energy
   in each band.  CELT uses a coarse-fine strategy for encoding the
   energy in the base-2 log domain, as implemented in quant_bands.c

5.3.4.1.  Coarse energy quantization

   The coarse quantization of the energy uses a fixed resolution of 6
   dB.  To minimize the bitrate, prediction is applied both in time
   (using the previous frame) and in frequency (using the previous
   bands).  The prediction using the previous frame can be disabled,
   creating an "intra" frame where the energy is coded without reference
   to prior frames.  An encoder is able to choose the mode used at will
   based on both loss robustness and efficiency considerations.  The 2-D
   z-transform of the prediction filter is: A(z_l, z_b)=(1-a*z_l^-1)*(1-
   z_b^-1)/(1-b*z_b^-1) where b is the band index and l is the frame
   index.  The prediction coefficients applied depend on the frame size
   in use when not using intra energy and a=0 b=4915/32768 when using
   intra energy.  The time-domain prediction is based on the final fine
   quantization of the previous frame, while the frequency domain
   (within the current frame) prediction is based on coarse quantization
   only (because the fine quantization has not been computed yet).  The
   prediction is clamped internally so that fixed point implementations
   with limited dynamic range to not suffer desynchronization.
   Identical prediction clamping must be implemented in all encoders and
   decoders.  We approximate the ideal probability distribution of the
   prediction error using a Laplace distribution with seperate
   parameters for each frame size in intra and inter-frame modes.  The
   coarse energy quantization is performed by quant_coarse_energy() and
   quant_coarse_energy() (quant_bands.c).  The encoding of the Laplace-
   distributed values is implemented in ec_laplace_encode() (laplace.c).

5.3.4.2.  Fine energy quantization

   After the coarse energy quantization and encoding, the bit allocation
   is computed (Section 4.3.3) and the number of bits to use for
   refining the energy quantization is determined for each band.  Let



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   B_i be the number of fine energy bits for band i; the refinement is
   an integer f in the range [0,2^B_i-1].  The mapping between f and the
   correction applied to the coarse energy is equal to (f+1/2)/2^B_i -
   1/2.  Fine energy quantization is implemented in quant_fine_energy()
   (quant_bands.c).

   If any bits are unused at the end of the encoding process, these bits
   are used to increase the resolution of the fine energy encoding in
   some bands.  Priority is given to the bands for which the allocation
   (Section 4.3.3) was rounded down.  At the same level of priority,
   lower bands are encoded first.  Refinement bits are added until there
   is no more room for fine energy or until each band has gained an
   additional bit of precision or has the maximum fine energy precision.
   This is implemented in quant_energy_finalise() (quant_bands.c).

5.3.5.  Spherical Vector Quantization

   CELT uses a Pyramid Vector Quantization (PVQ) [PVQ] codebook for
   quantizing the details of the spectrum in each band that have not
   been predicted by the pitch predictor.  The PVQ codebook consists of
   all sums of K signed pulses in a vector of N samples, where two
   pulses at the same position are required to have the same sign.  Thus
   the codebook includes all integer codevectors y of N dimensions that
   satisfy sum(abs(y(j))) = K.

   In bands where there are sufficient bits allocated the PVQ is used to
   encode the unit vector that results from the normalization in
   Section 5.3.3 directly.  Given a PVQ codevector y, the unit vector X
   is obtained as X = y/||y||, where ||.|| denotes the L2 norm.

5.3.5.1.  PVQ Search

   The search for the best codevector y is performed by alg_quant()
   (vq.c).  There are several possible approaches to the search with a
   tradeoff between quality and complexity.  The method used in the
   reference implementation computes an initial codeword y1 by
   projecting the residual signal R = X - p' onto the codebook pyramid
   of K-1 pulses:

   y0 = round_towards_zero( (K-1) * R / sum(abs(R)))

   Depending on N, K and the input data, the initial codeword y0 may
   contain from 0 to K-1 non-zero values.  All the remaining pulses,
   with the exception of the last one, are found iteratively with a
   greedy search that minimizes the normalized correlation between y and
   R:

   J = -R^T*y / ||y||



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   The search described above is considered to be a good trade-off
   between quality and computational cost.  However, there are other
   possible ways to search the PVQ codebook and the implementors MAY use
   any other search methods.

5.3.5.2.  Index Encoding

   The best PVQ codeword is encoded as a uniformly-distributed integer
   value by encode_pulses() (cwrs.c).  The codeword is converted from a
   unique index in the same way as specified in [PVQ].  The indexing is
   based on the calculation of V(N,K) (denoted N(L,K) in [PVQ]), which
   is the number of possible combinations of K pulses in N samples.

5.3.6.  Stereo support

   When encoding a stereo stream, some parameters are shared across the
   left and right channels, while others are transmitted separately for
   each channel, or jointly encoded.  Only one copy of the flags for the
   features, transients and pitch (pitch period and filter parameters)
   are transmitted.  The coarse and fine energy parameters are
   transmitted separately for each channel.  Both the coarse energy and
   fine energy (including the remaining fine bits at the end of the
   stream) have the left and right bands interleaved in the stream, with
   the left band encoded first.

   The main difference between mono and stereo coding is the PVQ coding
   of the normalized vectors.  In stereo mode, a normalized mid-side
   (M-S) encoding is used.  Let L and R be the normalized vector of a
   certain band for the left and right channels, respectively.  The mid
   and side vectors are computed as M=L+R and S=L-R and no longer have
   unit norm.

   From M and S, an angular parameter theta=2/pi*atan2(||S||, ||M||) is
   computed.  The theta parameter is converted to a Q14 fixed-point
   parameter itheta, which is quantized on a scale from 0 to 1 with an
   interval of 2^-qb, where qb is based the number of bits allocated to
   the band.  From here on, the value of itheta MUST be treated in a
   bit-exact manner since both the encoder and decoder rely on it to
   infer the bit allocation.

   Let m=M/||M|| and s=S/||S||; m and s are separately encoded with the
   PVQ encoder described in Section 5.3.5.  The number of bits allocated
   to m and s depends on the value of itheta.

5.3.7.  Synthesis

   After all the quantization is completed, the quantized energy is used
   along with the quantized normalized band data to resynthesize the



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   MDCT spectrum.  The inverse MDCT (Section 4.3.7) and the weighted
   overlap-add are applied and the signal is stored in the _synthesis
   buffer_.  The encoder MAY omit this step of the processing if it does
   not need the decoded output.

5.3.8.  Variable Bitrate (VBR)

   Each CELT frame can be encoded in a different number of octets,
   making it possible to vary the bitrate at will.  This property can be
   used to implement source-controlled variable bitrate (VBR).  Support
   for VBR is OPTIONAL for the encoder, but a decoder MUST be prepared
   to decode a stream that changes its bit-rate dynamically.  The method
   used to vary the bit-rate in VBR mode is left to the implementor, as
   long as each frame can be decoded by the reference decoder.





































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6.  Conformance

   It is the intention to allow the greatest possible choice of freedom
   in implementing the specification.  For this reason, outside of a few
   exceptions noted in this section, conformance is defined through the
   reference implementation of the decoder provided in Appendix
   Appendix A.  Although this document includes an English description
   of the codec, should the description contradict the source code of
   the reference implementation, the latter shall take precedence.

   Compliance with this specification means that a decoder's output MUST
   be within the thresholds specified compared to the reference
   implementation using the opus_compare.m tool in Appendix Appendix B.






































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7.  Security Considerations

   The codec needs to take appropriate security considerations into
   account, as outlined in [DOS] and [SECGUIDE].  It is extremely
   important for the decoder to be robust against malicious payloads.
   Malicious payloads must not cause the decoder to overrun its
   allocated memory or to take much more resources to decode.  Although
   problems in encoders are typically rarer, the same applies to the
   encoder.  Malicious audio stream must not cause the encoder to
   misbehave because this would allow an attacker to attack transcoding
   gateways.

   The reference implementation contains no known buffer overflow or
   cases where a specially crafter packet or audio segment could cause a
   significant increase in CPU load.  However, on certain CPU
   architectures where denormalized floating-point operations are much
   slower it is possible for some audio content (e.g. silence or near-
   silence) to cause such an increase in CPU load.  For such
   architectures, it is RECOMMENDED to add very small floating-point
   offsets to prevent significant numbers of denormalized operations or
   to configure the hardware to zeroize denormal numbers.  No such issue
   exists for the fixed-point reference implementation.





























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8.  IANA Considerations

   This document has no actions for IANA.
















































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9.  Acknowledgments

   Thanks to all other developers, including Raymond Chen, Soeren Skak
   Jensen, Gregory Maxwell, Christopher Montgomery, Karsten Vandborg
   Soerensen, and Timothy Terriberry.














































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10.  Informative References

   [SILK]     Vos, K., Jensen, S., and K. Soerensen, "SILK Speech
              Codec", draft-vos-silk-01 (work in progress), March 2010.

   [laroia-icassp]
              Laroia, R., Phamdo, N., and N. Farvardin, "Robust and
              Efficient Quantization of Speech LSP Parameters Using
              Structured Vector Quantization", ICASSP-1991, Proc. IEEE
              Int. Conf. Acoust., Speech, Signal Processing, pp. 641-
              644, October 1991.

   [sinervo-norsig]
              Sinervo, U., Nurminen, J., Heikkinen, A., and J. Saarinen,
              "Evaluation of Split and Multistage Techniques in LSF
              Quantization", NORSIG-2001, Norsk symposium i
              signalbehandling, Trondheim, Norge, October 2001.

   [leblanc-tsap]
              LeBlanc, W., Bhattacharya, B., Mahmoud, S., and V.
              Cuperman, "Efficient Search and Design Procedures for
              Robust Multi-Stage VQ of LPC Parameters for 4 kb/s Speech
              Coding", IEEE Transactions on Speech and Audio Processing,
              Vol. 1, No. 4, October 1993.

   [CELT]     Valin, J-M., Terriberry, T., Maxwell, G., and C.
              Montgomery, "Constrained-Energy Lapped Transform (CELT)
              Codec", draft-valin-celt-codec-02 (work in progress),
              July 2010.

   [DOS]      Handley, M., Rescorla, E., and IAB, "Internet Denial-of-
              Service Considerations", RFC 4732, December 2006.

   [SECGUIDE]
              Rescorla, E. and B. Korver, "Guidelines for Writing RFC
              Text on Security Considerations", BCP 72, RFC 3552,
              July 2003.

   [range-coding]
              Nigel, G. and N. Martin, "Range encoding: An algorithm for
              removing redundancy from a digitised message", Proc.
              Institution of Electronic and Radio Engineers
              International Conference on Video and Data Recording ,
              1979.

   [coding-thesis]
              Pasco, R., "Source coding algorithms for fast data
              compression", Ph.D. thesis Dept. of Electrical



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              Engineering, Stanford University, May 1976.

   [PVQ]      Fischer, T., "A Pyramid Vector Quantizer", IEEE Trans. on
              Information Theory, Vol. 32 pp. 568-583, July 1986.

   [1]  <http://developer.skype.com/silk>

   [2]  <http://www.celt-codec.org/>

   [3]  <git://git.xiph.org/users/jm/ietfcodec.git>









































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Appendix A.  Reference Implementation

   This appendix contains the complete source code for the reference
   implementation of the Opus codec written in C. This implementation
   can be compiled for either floating-point or fixed-point
   architectures.

   The implementation can be compiled with either a C89 or a C99
   compiler.  It is reasonably optimized for most platforms such that
   only architecture-specific optimizations are likely to be useful.
   The FFT used is a slightly modified version of the KISS-FFT package,
   but it is easy to substitute any other FFT library.

A.1.  Extracting the source

   The complete source code can be extracted from this draft, by running
   the following command line:

   o  cat draft-ietf-codec-opus.txt | grep '^\ \ \ ###' | sed
      's/\s\s\s###//' | base64 -d > opus_source.tar.gz

   o  tar xzvf opus_source.tar.gz

   o  cd opus_source

   o  make

A.2.  Base64-encoded source code

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Valin & Vos            Expires September 15, 2011              [Page 57]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 58]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 59]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 61]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 62]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 63]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 64]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 65]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 66]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 67]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 68]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 70]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 71]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 72]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 73]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 74]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 75]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 78]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 79]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 80]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 81]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 83]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 84]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 85]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 86]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 87]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 89]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 90]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 92]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 93]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 94]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 95]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 96]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 97]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 98]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011              [Page 99]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 103]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 104]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 105]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 106]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 107]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 108]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 109]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 112]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 115]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 116]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 117]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 118]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 120]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 121]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 122]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 123]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 124]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 125]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 126]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 127]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 128]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 129]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 130]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 133]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 136]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 137]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 138]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 139]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 140]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 141]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 142]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 143]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 146]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 148]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 149]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 152]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 154]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 155]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 156]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 157]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 158]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 159]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 160]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 161]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 162]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 163]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 164]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 165]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 166]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 167]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 169]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 170]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 171]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 172]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 173]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 174]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 175]


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Valin & Vos            Expires September 15, 2011             [Page 176]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 177]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 179]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 180]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 183]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 186]


Internet-Draft           Interactive Audio Codec              March 2011


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Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 188]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 189]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 190]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 191]


Internet-Draft           Interactive Audio Codec              March 2011


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Valin & Vos            Expires September 15, 2011             [Page 192]


Internet-Draft           Interactive Audio Codec              March 2011


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Appendix B.  opus_compare.m



   %% Tests bit-stream compliance for the Opus codec
   %% x: Signal from the Opus reference implementation (float or fixed)
   %% y: Signal from the decoder under test
   %% stereo: 0 for mono, 1 for stereo
   function [err, NMR] = opus_compare(x, y, stereo)

   % Bands on which we compute the pseudo-NMR (Bark-derived CELT bands)
   b = 2*[0,1,2,3,4,5,6,7,8,10,12,14,16,20,24,28,34,40,48,60,78,100];
   d = diff(b);

   % Per-band SNR threshold
   T = 50-.7*[1:21];

   % Noise floor
   N = 10 .^ ((10-0.6*[1:21])/10);

   % Error signal
   e=x-y;

   %Add a +/- 1 dead zone on the error
   e = e - min(1, max(-1, e));

   % Compute spectrum of original and error
   if (stereo)
     X=(abs(specgram(x(1:2:end),480))+abs(specgram(x(2:2:end),480)))/2;
     E=(abs(specgram(e(1:2:end),480))+abs(specgram(e(2:2:end),480)))/2;
   else
     X=abs(specgram(x,480));
     E=abs(specgram(e,480));
   endif

   % Group energy per band
   for k=1:21
      Xb(k,:) = sum(X(b(k)+1:b(k+1),:).^2)/d(k)+1;
      Eb(k,:) = sum(E(b(k)+1:b(k+1),:).^2)/d(k)+1;
   end

   % Frequency masking (low to high) with 10 dB/Bark slope
   Xb = filter(1, [1, -.1], Xb);
   % Frequency masking (high to low) with 15 dB/Bark slope
   Xb(end:-1:1,:) = filter(1, [1, -.03], Xb(end:-1:1,:));

   % Temporal masking with 5 dB/5 ms slope
   Xb = filter(1, [1, -.3], Xb')';



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   % NMR threshold
   T0 = ones(length(Eb), 1)*(10.^((T)/10));

   % Time-frequency SNR
   NMR = (Xb./Eb)';

   %Picking only errors in the 90th percentile
   tmp = Eb(:);
   thresh = sort(tmp)(round(.90*length(tmp)));
   weight = Eb'>thresh;

   printf("Average pseudo-NMR: %3.2f dB\n", mean(mean(10*log10(NMR))));

   if (sum(sum(weight))<1)
      printf("Mismatch level: below noise floor\n");
      err = -100;
   else
      M = (T0./NMR) .* weight;

      err = 10*log10(sum(sum(M)) / sum(sum(weight)));

      printf("Weighted mismatch: %3.2f dB\n", err);
   endif

   printf("\n");

   if (err < 0)
      printf("**Decoder PASSES test (mismatch < 0 dB)\n");
   else
      printf("**Decoder FAILS test (mismatch >= 0 dB)\n");
   endif




















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Internet-Draft           Interactive Audio Codec              March 2011


Authors' Addresses

   Jean-Marc Valin
   Octasic Inc.
   4101, Molson Street
   Montreal, Quebec
   Canada

   Phone: +1 514 282-8858
   Email: jean-marc.valin@octasic.com


   Koen Vos
   Skype Technologies S.A.
   Stadsgarden 6
   Stockholm,   11645
   SE

   Phone: +46 855 921 989
   Email: koen.vos@skype.net































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